UC3842B, UC3843B, UC2842B, UC2843B High Performance Current Mode Controllers The UC3842B, UC3843B series are high performance fixed frequency current mode controllers. They are specifically designed for Off–Line and dc–to–dc converter applications offering the designer a cost–effective solution with minimal external components. These integrated circuits feature a trimmed oscillator for precise duty cycle control, a temperature compensated reference, high gain error amplifier, current sensing comparator, and a high current totem pole output ideally suited for driving a power MOSFET. Also included are protective features consisting of input and reference undervoltage lockouts each with hysteresis, cycle–by–cycle current limiting, programmable output deadtime, and a latch for single pulse metering. These devices are available in an 8–pin dual–in–line and surface mount (SO–8) plastic package as well as the 14–pin plastic surface mount (SO–14). The SO–14 package has separate power and ground pins for the totem pole output stage. The UCX842B has UVLO thresholds of 16 V (on) and 10 V (off), ideally suited for off–line converters. The UCX843B is tailored for lower voltage applications having UVLO thresholds of 8.5 V (on) and 7.6 V (off). • Trimmed Oscillator for Precise Frequency Control • Oscillator Frequency Guaranteed at 250 kHz • Current Mode Operation to 500 kHz • Automatic Feed Forward Compensation • Latching PWM for Cycle–By–Cycle Current Limiting • Internally Trimmed Reference with Undervoltage Lockout • High Current Totem Pole Output • Undervoltage Lockout with Hysteresis • Low Startup and Operating Current VCC Vref 8(14) 5.0V Reference R 2(3) Output Compensation 1(1) 7(11) 6(10) Power Ground 5(8) Latching PWM Error Amplifier Current Sense 3(5) Input Gnd 8 1 SO–8 D1 SUFFIX CASE 751 8 1 SO–14 D SUFFIX CASE 751A 14 1 PIN CONNECTIONS Compensation Voltage Feedback Current Sense RT/CT 1 8 2 7 3 6 4 5 Vref VCC Output Gnd (Top View) Compensation NC Voltage Feedback NC Current Sense NC RT/CT 1 14 2 13 3 12 4 11 5 10 6 9 7 8 Vref NC VCC VC Output Gnd Power Ground (Top View) Output + - PDIP–8 N SUFFIX CASE 626 VC Oscillator 4(7) Voltage Feedback Input VCC Undervoltage Lockout Vref Undervoltage Lockout R RT/CT 7(12) http://onsemi.com ORDERING INFORMATION See detailed ordering and shipping information in the package dimensions section on page 16 of this data sheet. DEVICE MARKING INFORMATION See general marking information in the device marking section on page 17 of this data sheet. 5(9) Pin numbers in parenthesis are for the D suffix SO-14 package. Figure 1. Simplified Block Diagram Semiconductor Components Industries, LLC, 2001 April, 2001 – Rev. 2 1 Publication Order Number: UC3842B/D UC3842B, UC3843B, UC2842B, UC2843B MAXIMUM RATINGS Symbol Value Unit Bias and Driver Voltages (Zero Series Impedance, see also Total Device spec) Rating VCC, VC 30 V Total Power Supply and Zener Current (ICC + IZ) 30 mA IO 1.0 A Output Current, Source or Sink (Note 1.) Output Energy (Capacitive Load per Cycle) W 5.0 µJ Current Sense and Voltage Feedback Inputs Vin – 0.3 to + 5.5 V Error Amp Output Sink Current IO 10 mA PD RθJA 862 145 mW °C/W PD RθJA 702 178 mW °C/W PD RθJA 1.25 100 W °C/W Operating Junction Temperature TJ +150 °C Operating Ambient Temperature UC3842B, UC3843B UC2842B, UC2843B UC3842BV, UC3843BV TA Storage Temperature Range Tstg Power Dissipation and Thermal Characteristics D Suffix, Plastic Package, SO–14 Case 751A Maximum Power Dissipation @ TA = 25°C Thermal Resistance, Junction–to–Air D1 Suffix, Plastic Package, SO–8 Case 751 Maximum Power Dissipation @ TA = 25°C Thermal Resistance, Junction–to–Air N Suffix, Plastic Package, Case 626 Maximum Power Dissipation @ TA = 25°C Thermal Resistance, Junction–to–Air °C 0 to + 70 – 25 to + 85 –40 to +105 °C – 65 to +150 ELECTRICAL CHARACTERISTICS (VCC = 15 V [Note 2.], RT = 10 k, CT = 3.3 nF. For typical values TA = 25°C, for min/max values TA is the operating ambient temperature range that applies [Note 3.], unless otherwise noted.) UC284XB Characteristics UC384XB, XBV Symbol Min Typ Max Min Typ Max Unit Vref 4.95 5.0 5.05 4.9 5.0 5.1 V Line Regulation (VCC = 12 V to 25 V) Regline – 2.0 20 – 2.0 20 mV Load Regulation (IO = 1.0 mA to 20 mA) Regload – 3.0 25 – 3.0 25 mV mV/°C REFERENCE SECTION Reference Output Voltage (IO = 1.0 mA, TJ = 25°C) Temperature Stability TS – 0.2 – – 0.2 – Total Output Variation over Line, Load, and Temperature Vref 4.9 – 5.1 4.82 – 5.18 V Output Noise Voltage (f = 10 Hz to 10 kHz, TJ = 25°C) Vn – 50 – – 50 – µV Long Term Stability (TA = 125°C for 1000 Hours) Output Short Circuit Current S – 5.0 – – 5.0 – mV ISC – 30 – 85 –180 – 30 – 85 –180 mA 49 48 225 52 – 250 55 56 275 49 48 225 52 – 250 55 56 275 OSCILLATOR SECTION Frequency TJ = 25°C TA = Tlow to Thigh TJ = 25°C (RT = 6.2 k, CT = 1.0 nF) fOSC kHz Frequency Change with Voltage (VCC = 12 V to 25 V) ∆fOSC/∆V – 0.2 1.0 – 0.2 1.0 % Frequency Change with Temperature TA = Tlow to Thigh ∆fOSC/∆T – 1.0 – – 0.5 – % Oscillator Voltage Swing (Peak–to–Peak) VOSC – 1.6 – – 1.6 – V Discharge Current (VOSC = 2.0 V) TJ = 25°C TA = Tlow to Thigh (UC284XB, UC384XB) TA = Tlow to Thigh (UC384XBV) Idischg 7.8 7.5 – 8.3 – – 8.8 8.8 – 7.8 7.6 7.2 8.3 – – 8.8 8.8 8.8 mA 1. Maximum Package power dissipation limits must be observed. 2. Adjust VCC above the Startup threshold before setting to 15 V. 3. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. Thigh = +70°C for UC3842B, UC3843B Tlow = 0°C for UC3842B, UC3843B –25°C for UC2842B, UC2843B +85°C for UC2842B, UC2843B –40°C for UC3842BV, UC3843BV +105°C for UC3842BV, UC3843BV http://onsemi.com 2 UC3842B, UC3843B, UC2842B, UC2843B ELECTRICAL CHARACTERISTICS (VCC = 15 V [Note 4.], RT = 10 k, CT = 3.3 nF. For typical values TA = 25°C, for min/max values TA is the operating ambient temperature range that applies [Note 5.], unless otherwise noted.) UC284XB Characteristics UC384XB, XBV Symbol Min Typ Max Min Typ Max Unit VFB 2.45 2.5 2.55 2.42 2.5 2.58 V IIB – – 0.1 –1.0 – – 0.1 – 2.0 µA AVOL 65 90 – 65 90 – dB BW 0.7 1.0 – 0.7 1.0 – MHz PSRR 60 70 – 60 70 – dB ISink 2.0 – 0.5 12 –1.0 – – 2.0 – 0.5 12 –1.0 – – 5.0 6.2 – 5.0 6.2 – – – 0.8 – 1.1 – – – 0.8 0.8 1.1 1.2 2.85 – 3.0 – 3.15 – 2.85 2.85 3.0 3.0 3.15 3.25 0.9 – 1.0 – 1.1 – 0.9 0.85 1.0 1.0 1.1 1.1 PSRR – 70 – – 70 – dB ERROR AMPLIFIER SECTION Voltage Feedback Input (VO = 2.5 V) Input Bias Current (VFB = 5.0 V) Open Loop Voltage Gain (VO = 2.0 V to 4.0 V) Unity Gain Bandwidth (TJ = 25°C) Power Supply Rejection Ratio (VCC = 12 V to 25 V) Output Current Sink (VO = 1.1 V, VFB = 2.7 V) Source (VO = 5.0 V, VFB = 2.3 V) mA ISource Output Voltage Swing High State (RL = 15 k to ground, VFB = 2.3 V) Low State (RL = 15 k to Vref, VFB = 2.7 V) (UC284XB, UC384XB) (UC384XBV) V VOH VOL CURRENT SENSE SECTION Current Sense Input Voltage Gain (Notes 6. & 7.) (UC284XB, UC384XB) (UC384XBV) AV Maximum Current Sense Input Threshold (Note 6.) (UC284XB, UC384XB) (UC384XBV) Vth Power Supply Rejection Ratio (VCC = 12 V to 25 V, Note 6.) V/V V IIB – – 2.0 –10 – – 2.0 –10 µA tPLH(In/Out) – 150 300 – 150 300 ns Output Voltage Low State (ISink = 20 mA) (ISink = 200 mA) VOL High State VOH – – – 13 – 12 0.1 1.6 – 13.5 – 13.4 0.4 2.2 – – – – – – – 13 12.9 12 0.1 1.6 1.6 13.5 13.5 13.4 0.4 2.2 2.3 – – – VOL(UVLO) – 0.1 1.1 – 0.1 1.1 V Output Voltage Rise Time (CL = 1.0 nF, TJ = 25°C) tr – 50 150 – 50 150 ns Output Voltage Fall Time (CL = 1.0 nF, TJ = 25°C) tf – 50 150 – 50 150 ns 15 7.8 16 8.4 17 9.0 14.5 7.8 16 8.4 17.5 9.0 9.0 7.0 10 7.6 11 8.2 8.5 7.0 10 7.6 11.5 8.2 Input Bias Current Propagation Delay (Current Sense Input to Output) OUTPUT SECTION V (UC284XB, UC384XB) (UC384XBV) (ISource = 20 mA) (UC284XB, UC384XB) (UC384XBV) (ISource = 200 mA) Output Voltage with UVLO Activated (VCC = 6.0 V, ISink = 1.0 mA) UNDERVOLTAGE LOCKOUT SECTION Startup Threshold (VCC) UCX842B, BV UCX843B, BV Vth Minimum Operating Voltage After Turn–On (VCC) UCX842B, BV UCX843B, BV V VCC(min) V 4. Adjust VCC above the Startup threshold before setting to 15 V. 5. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. Tlow = 0°C for UC3842B, UC3843B Thigh = +70°C for UC3842B, UC3843B –25°C for UC2842B, UC2843B +85°C for UC2842B, UC2843B –40°C for UC3842BV, UC3843BV +105°C for UC3842BV, UC3843BV 6. This parameter is measured at the latch trip point with VFB = 0 V. 7. Comparator gain is defined as: AV ∆V Output Compensation ∆V Current Sense Input http://onsemi.com 3 UC3842B, UC3843B, UC2842B, UC2843B ELECTRICAL CHARACTERISTICS (VCC = 15 V [Note 8.], RT = 10 k, CT = 3.3 nF, for typical values TA = 25°C, for min/max values TA is the operating ambient temperature range that applies [Note 9.], unless otherwise noted.) UC284XB Characteristics UC384XB, BV Symbol Min Typ Max Min Typ Max DC(max) 94 – – 96 – – – – 0 94 93 – 96 96 – – – 0 – 0.3 0.5 – 0.3 0.5 – 12 17 – 12 17 30 36 – 30 36 – Unit PWM SECTION % Duty Cycle Maximum (UC284XB, UC384XB) Maximum (UC384XBV) Minimum DC(min) TOTAL DEVICE ICC + IC Power Supply Current Startup (VCC = 6.5 V for UCX843B, Startup (VCC 14 V for UCX842B, BV) Operating (Note 8.) Power Supply Zener Voltage (ICC = 25 mA) mA VZ V 8. Adjust VCC above the Startup threshold before setting to 15 V. 9. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. Thigh = +70°C for UC3842B, UC3843B Tlow = 0°C for UC3842B, UC3843B –25°C for UC2842B, UC2843B +85°C for UC2842B, UC2843B –40°C for UC3842BV, UC3843BV +105°C for UC3842BV, UC3843BV 80 100 % DT, PERCENT OUTPUT DEADTIME R T, TIMING RESISTOR (k Ω) 50 20 8.0 5.0 2.0 0.8 10 k VCC = 15 V TA = 25°C 20 k 50 k 100 k 200 k 500 k fOSC, OSCILLATOR FREQUENCY (kHz) 1. CT = 10 nF 50 2. CT = 5.0 nF 3. CT = 2.0 nF 4. CT = 1.0 nF 20 5. CT = 500 pF 6. CT = 200 pF 10 7. CT = 100 pF D max , MAXIMUM OUTPUT DUTY CYCLE (%) I dischg , DISCHARGE CURRENT (mA) VCC = 15 V VOSC = 2.0 V 8.5 8.0 7.5 0 25 50 75 TA, AMBIENT TEMPERATURE (°C) 6 7 VCC = 15 V TA = 25°C 2.0 20 k 50 k 100 k 200 k 500 k fOSC, OSCILLATOR FREQUENCY (kHz) 1.0 M Figure 3. Output Deadtime versus Oscillator Frequency 9.0 -25 1 5 Figure 2. Timing Resistor versus Oscillator Frequency 7.0 -55 3 2 5.0 1.0 10 k 1.0 M 4 100 125 100 90 80 Idischg = 7.5 mA 70 Idischg = 8.8 mA 60 50 40 0.8 Figure 4. Oscillator Discharge Current versus Temperature 1.0 2.0 3.0 4.0 RT, TIMING RESISTOR (kΩ) VCC = 15 V CT = 3.3 nF TA = 25°C 5.0 6.0 7.0 8.0 Figure 5. Maximum Output Duty Cycle versus Timing Resistor http://onsemi.com 4 UC3842B, UC3843B, UC2842B, UC2843B VCC = 15 V AV = -1.0 TA = 25°C 20 mV/DIV 2.50 V VCC = 15 V AV = -1.0 TA = 25°C 3.0 V 20 mV/DIV 2.55 V 2.5 V 2.45 V 2.0 V 0.5 µs/DIV 1.0 µs/DIV 80 Gain 60 40 Phase 0 30 60 90 20 120 0 150 100 10 k 100 k 180 10 M 1.0 M VCC = 15 V 1.0 0.8 TA = 25°C 0.6 TA = 125°C 0.4 TA = -55°C 0.2 0 0 2.0 4.0 6.0 VO, ERROR AMP OUTPUT VOLTAGE (V) Figure 8. Error Amp Open Loop Gain and Phase versus Frequency Figure 9. Current Sense Input Threshold versus Error Amp Output Voltage ÄÄÄÄ ÄÄÄ ÄÄÄÄ ÄÄÄ ÄÄÄÄ ÄÄÄÄ ÄÄÄÄ VCC = 15 V -4.0 -8.0 -12 TA = -55°C TA = 125°C -16 -20 TA = 25°C 0 1.2 f, FREQUENCY (Hz) 0 -24 1.0 k I SC , REFERENCE SHORT CIRCUIT CURRENT (mA) -20 10 ∆ Vref , REFERENCE VOLTAGE CHANGE (mV) VCC = 15 V VO = 2.0 V to 4.0 V RL = 100 K TA = 25°C φ, EXCESS PHASE (DEGREES) A VOL , OPEN LOOP VOLTAGE GAIN (dB) 100 Figure 7. Error Amp Large Signal Transient Response Vth, CURRENT SENSE INPUT THRESHOLD (V) Figure 6. Error Amp Small Signal Transient Response 20 40 60 80 100 120 8.0 ÄÄÄ ÄÄÄ 110 VCC = 15 V RL ≤ 0.1 Ω 90 70 50 -55 -25 0 25 50 75 100 Iref, REFERENCE SOURCE CURRENT (mA) TA, AMBIENT TEMPERATURE (°C) Figure 10. Reference Voltage Change versus Source Current Figure 11. Reference Short Circuit Current versus Temperature http://onsemi.com 5 125 ∆ V O , OUTPUT VOLTAGE CHANGE (2.0 mV/DIV ∆ V O , OUTPUT VOLTAGE CHANGE (2.0 mV/DIV UC3842B, UC3843B, UC2842B, UC2843B VCC = 15 V IO = 1.0 mA to 20 mA TA = 25°C 2.0 ms/DIV VCC = 12 V to 25 TA = 25°C 2.0 ms/DIV 0 -2.0 Source Saturation (Load to Ground) VCC = 15 V CL = 1.0 nF TA = 25°C 90% TA = -55°C 2.0 TA = 25°C 200 Gnd 400 600 10% 800 IO, OUTPUT LOAD CURRENT (mA) 50 ns/DIV Figure 14. Output Saturation Voltage versus Load Current Figure 15. Output Waveform V O , OUTPUT VOLTAGE 25 20 V/DIV 20 15 10 5 0 0 100 ns/DIV 10 ÄÄÄÄ ÄÄÄÄ ÄÄÄÄ ÄÄÄÄ RT = 10 k CT = 3.3 nF VFB = 0 V ISense = 0 V TA = 25°C UCX842B VCC = 30 V CL = 15 pF TA = 25°C UCX843B 0 Sink Saturation (Load to VCC) I CC , SUPPLY CURRENT (mA) 1.0 I CC , SUPPLY CURRENT VCC = 15 V 80 µs Pulsed Load 120 Hz Rate TA = -55°C 3.0 0 ÄÄÄÄÄ ÄÄÄÄÄ ÄÄÄ ÄÄÄÄ ÄÄÄÄÄ ÄÄÄÄÄ ÄÄÄÄ ÄÄÄÄÄ ÄÄÄÄ ÄÄÄ ÄÄÄ ÄÄÄÄ ÄÄÄ ÄÄÄ ÄÄÄÄ ÄÄ VCC TA = 25°C -1.0 Figure 13. Reference Line Regulation 100 mA/DIV Vsat, OUTPUT SATURATION VOLTAGE (V) Figure 12. Reference Load Regulation 20 30 40 VCC, SUPPLY VOLTAGE (V) Figure 16. Output Cross Conduction Figure 17. Supply Current versus Supply Voltage http://onsemi.com 6 UC3842B, UC3843B, UC2842B, UC2843B PIN FUNCTION DESCRIPTION Pin 8–Pin 14–Pin Function 1 1 Compensation 2 3 Voltage Feedback This is the inverting input of the Error Amplifier. It is normally connected to the switching power supply output through a resistor divider. 3 5 Current Sense A voltage proportional to inductor current is connected to this input. The PWM uses this information to terminate the output switch conduction. 4 7 RT/CT 6 10 Output 7 12 VCC This pin is the positive supply of the control IC. 8 14 Vref This is the reference output. It provides charging current for capacitor C T through resistor RT. 8 Power Ground 11 VC 9 Gnd This pin is the control circuitry ground return and is connected back to the power source ground. 2,4,6,13 NC No connection. These pins are not internally connected. 5 Gnd Description This pin is the Error Amplifier output and is made available for loop compensation. The Oscillator frequency and maximum Output duty cycle are programmed by connecting resistor RT to Vref and capacitor CT to ground. Operation to 500 kHz is possible. This pin is the combined control circuitry and power ground. This output directly drives the gate of a power MOSFET. Peak currents up to 1.0 A are sourced and sunk by this pin. This pin is a separate power ground return that is connected back to the power source. It is used to reduce the effects of switching transient noise on the control circuitry. The Output high state (VOH) is set by the voltage applied to this pin. With a separate power source connection, it can reduce the effects of switching transient noise on the control circuitry. http://onsemi.com 7 UC3842B, UC3843B, UC2842B, UC2843B OPERATING DESCRIPTION This occurs when the power supply is operating and the load is removed, or at the beginning of a soft–start interval (Figures 24, 25). The Error Amp minimum feedback resistance is limited by the amplifier’s source current (0.5 mA) and the required output voltage (VOH) to reach the comparator’s 1.0 V clamp level: The UC3842B, UC3843B series are high performance, fixed frequency, current mode controllers. They are specifically designed for Off–Line and dc–to–dc converter applications offering the designer a cost–effective solution with minimal external components. A representative block diagram is shown in Figure 18. Rf(min) ≈ Oscillator The oscillator frequency is programmed by the values selected for the timing components RT and CT. Capacitor CT is charged from the 5.0 V reference through resistor RT to approximately 2.8 V and discharged to 1.2 V by an internal current sink. During the discharge of CT, the oscillator generates an internal blanking pulse that holds the center input of the NOR gate high. This causes the Output to be in a low state, thus producing a controlled amount of output deadtime. Figure 2 shows RT versus Oscillator Frequency and Figure 3, Output Deadtime versus Frequency, both for given values of CT. Note that many values of RT and CT will give the same oscillator frequency but only one combination will yield a specific output deadtime at a given frequency. The oscillator thresholds are temperature compensated to within ±6% at 50 kHz. Also because of industry trends moving the UC384X into higher and higher frequency applications, the UC384XB is guaranteed to within ±10% at 250 kHz. These internal circuit refinements minimize variations of oscillator frequency and maximum output duty cycle. The results are shown in Figures 4 and 5. In many noise–sensitive applications it may be desirable to frequency–lock the converter to an external system clock. This can be accomplished by applying a clock signal to the circuit shown in Figure 21. For reliable locking, the free–running oscillator frequency should be set about 10% less than the clock frequency. A method for multi–unit synchronization is shown in Figure 22. By tailoring the clock waveform, accurate Output duty cycle clamping can be achieved. 3.0 (1.0 V) + 1.4 V = 8800 Ω 0.5 mA Current Sense Comparator and PWM Latch The UC3842B, UC3843B operate as a current mode controller, whereby output switch conduction is initiated by the oscillator and terminated when the peak inductor current reaches the threshold level established by the Error Amplifier Output/Compensation (Pin 1). Thus the error signal controls the peak inductor current on a cycle–by–cycle basis. The Current Sense Comparator PWM Latch configuration used ensures that only a single pulse appears at the Output during any given oscillator cycle. The inductor current is converted to a voltage by inserting the ground–referenced sense resistor RS in series with the source of output switch Q1. This voltage is monitored by the Current Sense Input (Pin 3) and compared to a level derived from the Error Amp Output. The peak inductor current under normal operating conditions is controlled by the voltage at pin 1 where: Ipk = V(Pin 1) – 1.4 V 3 RS Abnormal operating conditions occur when the power supply output is overloaded or if output voltage sensing is lost. Under these conditions, the Current Sense Comparator threshold will be internally clamped to 1.0 V. Therefore the maximum peak switch current is: Ipk(max) = 1.0 V RS When designing a high power switching regulator it becomes desirable to reduce the internal clamp voltage in order to keep the power dissipation of RS to a reasonable level. A simple method to adjust this voltage is shown in Figure 23. The two external diodes are used to compensate the internal diodes, yielding a constant clamp voltage over temperature. Erratic operation due to noise pickup can result if there is an excessive reduction of the Ipk(max) clamp voltage. A narrow spike on the leading edge of the current waveform can usually be observed and may cause the power supply to exhibit an instability when the output is lightly loaded. This spike is due to the power transformer interwinding capacitance and output rectifier recovery time. The addition of an RC filter on the Current Sense Input with a time constant that approximates the spike duration will usually eliminate the instability (refer to Figure 27). Error Amplifier A fully compensated Error Amplifier with access to the inverting input and output is provided. It features a typical dc voltage gain of 90 dB, and a unity gain bandwidth of 1.0 MHz with 57 degrees of phase margin (Figure 8). The non–inverting input is internally biased at 2.5 V and is not pinned out. The converter output voltage is typically divided down and monitored by the inverting input. The maximum input bias current is –2.0 µA which can cause an output voltage error that is equal to the product of the input bias current and the equivalent input divider source resistance. The Error Amp Output (Pin 1) is provided for external loop compensation (Figure 32). The output voltage is offset by two diode drops (≈1.4 V) and divided by three before it connects to the non–inverting input of the Current Sense Comparator. This guarantees that no drive pulses appear at the Output (Pin 6) when pin 1 is at its lowest state (VOL). http://onsemi.com 8 UC3842B, UC3843B, UC2842B, UC2843B VCC VCC Vref 2.5V RT CT R Output/ Compensation 1(1) (See Text) Output Q1 6(10) + 1.0mA S 2R R Error Amplifier VC 7(11) Vref UVLO Oscillator 4(7) Voltage Feedback Input 2(3) + - 3.6V + - VCC UVLO Internal Bias R 7(12) 36V Reference Regulator 8(14) Vin R 1.0V Q Power Ground PWM Latch Current Sense Comparator Gnd 5(8) Current Sense Input 3(5) 5(9) Pin numbers adjacent to terminals are for the 8-pin dual-in-line package. Pin numbers in parenthesis are for the D suffix SO-14 package. = Sink Only Positive True Logic Figure 18. Representative Block Diagram Capacitor CT Latch Set" Input Output/ Compensation Current Sense Input Latch Reset" Input Output Small RT/Large CT Large RT/Small CT Figure 19. Timing Diagram http://onsemi.com 9 RS UC3842B, UC3843B, UC2842B, UC2843B Undervoltage Lockout Design Considerations Two undervoltage lockout comparators have been incorporated to guarantee that the IC is fully functional before the output stage is enabled. The positive power supply terminal (VCC) and the reference output (Vref) are each monitored by separate comparators. Each has built–in hysteresis to prevent erratic output behavior as their respective thresholds are crossed. The VCC comparator upper and lower thresholds are 16 V/10 V for the UCX842B, and 8.4 V/7.6 V for the UCX843B. The Vref comparator upper and lower thresholds are 3.6 V/3.4 V. The large hysteresis and low startup current of the UCX842B makes it ideally suited in off–line converter applications where efficient bootstrap startup techniques are required (Figure 34). The UCX843B is intended for lower voltage dc–to–dc converter applications. A 36 V zener is connected as a shunt regulator from VCC to ground. Its purpose is to protect the IC from excessive voltage that can occur during system startup. The minimum operating voltage (VCC) for the UCX842B is 11 V and 8.2 V for the UCX843B. These devices contain a single totem pole output stage that was specifically designed for direct drive of power MOSFETs. It is capable of up to ±1.0 A peak drive current and has a typical rise and fall time of 50 ns with a 1.0 nF load. Additional internal circuitry has been added to keep the Output in a sinking mode whenever an undervoltage lockout is active. This characteristic eliminates the need for an external pull–down resistor. The SO–14 surface mount package provides separate pins for VC (output supply) and Power Ground. Proper implementation will significantly reduce the level of switching transient noise imposed on the control circuitry. This becomes particularly useful when reducing the Ipk(max) clamp level. The separate VC supply input allows the designer added flexibility in tailoring the drive voltage independent of VCC. A zener clamp is typically connected to this input when driving power MOSFETs in systems where VCC is greater than 20 V. Figure 26 shows proper power and control ground connections in a current–sensing power MOSFET application. Do not attempt to construct the converter on wire–wrap or plug–in prototype boards. High frequency circuit layout techniques are imperative to prevent pulse–width jitter. This is usually caused by excessive noise pick–up imposed on the Current Sense or Voltage Feedback inputs. Noise immunity can be improved by lowering circuit impedances at these points. The printed circuit layout should contain a ground plane with low–current signal and high–current switch and output grounds returning on separate paths back to the input filter capacitor. Ceramic bypass capacitors (0.1 µF) connected directly to VCC, VC, and Vref may be required depending upon circuit layout. This provides a low impedance path for filtering the high frequency noise. All high current loops should be kept as short as possible using heavy copper runs to minimize radiated EMI. The Error Amp compensation circuitry and the converter output voltage divider should be located close to the IC and as far as possible from the power switch and other noise–generating components. Current mode converters can exhibit subharmonic oscillations when operating at a duty cycle greater than 50% with continuous inductor current. This instability is independent of the regulator’s closed loop characteristics and is caused by the simultaneous operating conditions of fixed frequency and peak current detecting. Figure 20A shows the phenomenon graphically. At t0, switch conduction begins, causing the inductor current to rise at a slope of m1. This slope is a function of the input voltage divided by the inductance. At t1, the Current Sense Input reaches the threshold established by the control voltage. This causes the switch to turn off and the current to decay at a slope of m2, until the next oscillator cycle. The unstable condition can be shown if a perturbation is added to the control voltage, resulting in a small ∆I (dashed line). With a fixed oscillator period, the current decay time is reduced, and the minimum current at switch turn–on (t2) is increased by ∆I + ∆I m2/m1. The minimum current at the next cycle (t3) decreases to (∆I + ∆I m2/m1) (m2/m1). This perturbation is multiplied by m2/m1 on each succeeding cycle, alternately increasing and decreasing the inductor current at switch turn–on. Several oscillator cycles may be required before the inductor current reaches zero causing the process to commence again. If m2/m1 is greater than 1, the converter will be unstable. Figure 20B shows that by adding an artificial ramp that is synchronized with the PWM clock to the control voltage, the ∆I perturbation will decrease to zero on succeeding cycles. This compensating ramp (m3) must have a slope equal to or slightly greater than m2/2 for stability. With m2/2 slope compensation, the average inductor current follows the control voltage, yielding true current mode operation. The compensating ramp can be derived from the oscillator and added to either the Voltage Feedback or Current Sense inputs (Figure 33). Reference The 5.0 V bandgap reference is trimmed to ±1.0% tolerance at TJ = 25°C on the UC284XB, and ±2.0% on the UC384XB. Its primary purpose is to supply charging current to the oscillator timing capacitor. The reference has short– circuit protection and is capable of providing in excess of 20 mA for powering additional control system circuitry. http://onsemi.com 10 UC3842B, UC3843B, UC2842B, UC2843B (A) ∆I Control Voltage m2 m1 Inductor Current l l m2 m1 l l m2 m2 m1 m1 Oscillator Period t0 t1 Vref 8(14) t2 External Sync Input m3 ∆I m1 Bias RT t3 (B) Control Voltage R 0.01 Osc 4(7) CT + 2R 2(3) 47 m2 R Inductor Current R EA 1(1) Oscillator Period t4 5(9) t5 The diode clamp is required if the Sync amplitude is large enough to cause the bottom side of CT to go more than 300 mV below ground. t6 Figure 20. Continuous Current Waveforms Figure 21. External Clock Synchronization VCC Vin 7(12) 5.0V Ref 8(14) 8(14) RA RB 6 3 5.0k 2 C R Q 2R S 5.0k MC1455 2(3) EA 1(1) f 1.44 (RA 2RB)C D(max) RB RA 2RB R 2R R EA 1.0V R R1 5(9) To Additional UCX84XBs Figure 22. External Duty Cycle Clamp and Multi–Unit Synchronization S 1.0 mA 2(3) 1 6(10) VClamp + R2 + 7 Q1 Osc 4(7) Osc 4(7) 7(11) + - R 4 5.0k + - Bias R Bias 8 R 5 R Q 5(8) Comp/Latch 3(5) 1(1) 5(9) VClamp ≈ 1.67 R2 1 R1 + 0.33x10-3 R1R1R2R2 Where: 0 ≤ VClamp ≤ 1.0 V Ipk(max) VClamp RS Figure 23. Adjustable Reduction of Clamp Level http://onsemi.com 11 RS UC3842B, UC3843B, UC2842B, UC2843B VCC Vin 7(12) 5.0V Ref 8(14) Bias 5.0V Ref 8(14) R R 1.0 mA EA 1.0M Q C 1.0V R1 3(5) MPSA63 1.67 RR21 1 5(9) tSoft-Start ≈ 3600C in µF tSoftStart In 1 Figure 24. Soft–Start Circuit VPin 5 (12) Where: 0 ≤ VClamp ≤ 1.0 V VC R1R2 C R1 R2 3VClamp 5.0V Ref RS Ipk rDS(on) rDM(on) RS VClamp RS VCC D (11) (10) 5.0V Ref + - SENSEFET S G 7(11) + - K Q1 M 6(10) S Q S (8) R Comp/Latch RS 1/4 W Vin 7(12) Then : VPin5 0.075Ipk + - (5) Ipk(max) Figure 25. Adjustable Buffered Reduction of Clamp Level with Soft–Start If: SENSEFET = MTP10N10M RS = 200 R RS Vin VCC + - 5(8) Comp/Latch 5(9) VClamp 1(1) C Q 1(1) R 2R R 1.0V R2 S 1.0mA 6(10) S R 2R R EA 2(3) + 2(3) VClamp + Osc 4(7) Q1 Osc 4(7) + - 7(11) + - Bias R + - R Power Ground: To Input Source Return Comp/Latch Q 5(8) 3(5) R C Control Circuitry Ground: To Pin (9) Virtually lossless current sensing can be achieved with the implementation of a SENSEFET power switch. For proper operation during over-current conditions, a reduction of the Ipk(max) clamp level must be implemented. Refer to Figures 23 and 25. RS The addition of the RC filter will eliminate instability caused by the leading edge spike on the current waveform. Figure 26. Current Sensing Power MOSFET Figure 27. Current Waveform Spike Suppression http://onsemi.com 12 UC3842B, UC3843B, UC2842B, UC2843B VCC Vin IB 7(12) Vin + 0 5.0V Ref + - Base Charge Removal 7(11) + - C1 Rg Q1 Q1 6(10) 6(10) S Q R 5(8) 5(8) Comp/Latch 3(5) RS 3(5) Series gate resistor Rg will damp any high frequency parasitic oscillations caused by the MOSFET input capacitance and any series wiring inductance in the gate-source circuit. The totem pole output can furnish negative base current for enhanced transistor turn-off, with the addition of capacitor C1. Figure 28. MOSFET Parasitic Oscillations Figure 29. Bipolar Transistor Drive Vin VCC 8(14) R Isolation Boundary 5.0V Ref Q1 + 0 50% DC 6(10) Comp/Latch 0 - 2(3) 25% DC 5(8) V(Pin1) 1.4 NS Ipk Np 3RS R 3(5) C RS NS 1.0 mA + - Q + VGS Waveforms 7(11) S Osc 4(7) + - + - R Bias 7(12) R RS EA 2R R 1(1) MCR 101 2N 3905 5(9) 2N 3903 NP The MCR101 SCR must be selected for a holding of < 0.5 mA @ TA(min). The simple two transistor circuit can be used in place of the SCR as shown. All resistors are 10 k. Figure 30. Isolated MOSFET Drive Figure 31. Latched Shutdown http://onsemi.com 13 UC3842B, UC3843B, UC2842B, UC2843B From VO 2.5V Ri + 1.0mA 2R 2(3) Cf Rd EA Rf R 1(1) Rf ≥ 8.8 k 5(9) Error Amp compensation circuit for stabilizing any current mode topology except for boost and flyback converters operating with continuous inductor current. From VO Rp Cp 2.5V Ri + 1.0mA 2(3) Cf Rd 2R R EA Rf 1(1) 5(9) Error Amp compensation circuit for stabilizing current mode boost and flyback topologies operating with continuous inductor current. Figure 32. Error Amplifier Compensation VCC Vin 7(12) 36V 8(14) RT MPS3904 RSlope From VO CT Ri Rd 5.0V Ref R R + - Rf 1(1) 7(11) Osc 4(7) + 2(3) Cf + - Bias EA 1.0mA -m S 2R R R 1.0V 6(10) Q Comp/Latch m - 3.0m 5(9) The buffered oscillator ramp can be resistively summed with either the voltage feedback or current sense inputs to provide slope compensation. Figure 33. Slope Compensation http://onsemi.com 14 5(8) 3(5) RS UC3842B, UC3843B, UC2842B, UC2843B + MDA 202 4.7k 250 3300 pF 56k 115 Vac 1N4935 7(12) + 8(14) 10k 68 4.7k 100 pF 6(10) R EA 150k 3(5) 470pF Figure 34. 27 W Off–Line Flyback Regulator Results Line Regulation: 5.0 V ±12 V Vin = 95 to 130 Vac ∆ = 50 mV or ± 0.5% ∆ = 24 mV or ± 0.1% Load Regulation: 5.0 V Vin = 115 Vac, Iout = 1.0 A to 4.0 A Vin = 115 Vac, Iout = 100 mA to 300 mA ∆ = 300 mV or ± 3.0% ±12 V Efficiency MTP 4N50 1N5819 1.0k 5(9) Output Ripple: 2.7k 5(8) Comp/Latch Conditions 5.0 V ±12 V 5.0V/4.0A 5.0V RTN + L2 10 + 12V/0.3A ±12V RTN 1000 Q 1(1) Test 1000 + 22 S 2(3) + MUR110 680pF + + 1000 MUR110 + 10 + -12V/0.3A L3 7(11) Osc 4(7) 4700pF 18k + 47 + - Bias R 2200 1N4937 5.0V Ref R T1 1N4935 100 0.01 L1 MBR1635 4.7Ω ∆ = 60 mV or ± 0.25% Vin = 115 Vac 40 mVpp 80 mVpp Vin = 115 Vac 70% All outputs are at nominal load currents, unless otherwise noted http://onsemi.com 15 0.5 1N4937 L1 - 15 µH at 5.0 A, Coilcraft Z7156 L2, L3 - 25 µH at 5.0 A, Coilcraft Z7157 T1 - Primary: 45 Turns #26 AWG Secondary ±12 V: 9 Turns #30 AWG (2 Strands) Bifiliar Wound Secondary 5.0 V: 4 Turns (six strands) #26 Hexfiliar Wound Secondary Feedback: 10 Turns #30 AWG (2 strands) Bifiliar Wound Core: Ferroxcube EC35-3C8 Bobbin: Ferroxcube EC35PCB1 Gap: ≈ 0.10" for a primary inductance of 1.0 mH UC3842B, UC3843B, UC2842B, UC2843B ORDERING INFORMATION Device Operating Temperature Range Package Shipping UC384XBD SO–14 55 Units/Rail UC384XBDR2 SO–14 2500 Tape & Reel UC384XBD1 SO–8 98 Units/Rail SO–8 2500 Tape & Reel UC384XBN PDIP–8 50 Units/Rail UC3842BN1 PDIP–8 50 Units/Rail UC284XBD SO–14 55 Units/Rail UC2843BDR2 SO–14 2500 Tape & Reel UC384XBD1R2 UC284XBD1 TA = 0° to +70°C SO–8 98 Units/Rail SO–8 2500 Tape & Reel UC284XBN PDIP–8 50 Units/Rail UC3843BVD SO–14 55 Units/Rail UC384XBVDR2 SO–14 2500 Tape & Reel SO–8 98 Units/Rail SO–8 2500 Tape & Reel PDIP–8 50 Units/Rail TA = –25° to +85°C UC284XBD1R2 UC384XBVD1 TA = –40° to +105°C UC384XBVD1R2 UC3843BVN X indicates either a 2 or 3 to define specific device part numbers. http://onsemi.com 16 UC3842B, UC3843B, UC2842B, UC2843B MARKING DIAGRAMS PDIP–8 N SUFFIX CASE 626 8 8 UC384xBN FAWL YYWW 8 UC3843BVN AWL YYWW 1 UC284xBN AWL YYWW 1 1 SO–8 D1 SUFFIX CASE 751 8 8 384xB ALYW 8 384xB ALYWV 1 1 284xB ALYW 1 SO–14 D SUFFIX CASE 751A 14 14 UC384xBD AWLYWW 1 14 UC384xBVD AWLYWW 1 UC284xBD AWLYWW 1 x A WL, L YY, Y WW, W = 2 or 3 = Assembly Location = Wafer Lot = Year = Work Week http://onsemi.com 17 UC3842B, UC3843B, UC2842B, UC2843B PACKAGE DIMENSIONS PDIP–8 N SUFFIX CASE 626–05 ISSUE L 8 NOTES: 1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL. 2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS). 3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 5 –B– 1 4 DIM A B C D F G H J K L M N F –A– NOTE 2 L C J –T– MILLIMETERS MIN MAX 9.40 10.16 6.10 6.60 3.94 4.45 0.38 0.51 1.02 1.78 2.54 BSC 0.76 1.27 0.20 0.30 2.92 3.43 7.62 BSC --10 0.76 1.01 INCHES MIN MAX 0.370 0.400 0.240 0.260 0.155 0.175 0.015 0.020 0.040 0.070 0.100 BSC 0.030 0.050 0.008 0.012 0.115 0.135 0.300 BSC --10 0.030 0.040 N SEATING PLANE D M K G H 0.13 (0.005) M T A M B M SO–8 D1 SUFFIX CASE 751–07 ISSUE W –X– NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. A 8 5 0.25 (0.010) S B 1 M Y M 4 K –Y– G C N X 45 SEATING PLANE –Z– 0.10 (0.004) H M D 0.25 (0.010) M Z Y S X S http://onsemi.com 18 J DIM A B C D G H J K M N S MILLIMETERS MIN MAX 4.80 5.00 3.80 4.00 1.35 1.75 0.33 0.51 1.27 BSC 0.10 0.25 0.19 0.25 0.40 1.27 0 8 0.25 0.50 5.80 6.20 INCHES MIN MAX 0.189 0.197 0.150 0.157 0.053 0.069 0.013 0.020 0.050 BSC 0.004 0.010 0.007 0.010 0.016 0.050 0 8 0.010 0.020 0.228 0.244 UC3842B, UC3843B, UC2842B, UC2843B PACKAGE DIMENSIONS SO–14 D SUFFIX CASE 751A–03 ISSUE F NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. –A– 14 8 –B– 1 P 7 PL 0.25 (0.010) 7 G B M M F R X 45 C –T– SEATING PLANE D 14 PL 0.25 (0.010) M K M T B S A S http://onsemi.com 19 J DIM A B C D F G J K M P R MILLIMETERS MIN MAX 8.55 8.75 3.80 4.00 1.35 1.75 0.35 0.49 0.40 1.25 1.27 BSC 0.19 0.25 0.10 0.25 0 7 5.80 6.20 0.25 0.50 INCHES MIN MAX 0.337 0.344 0.150 0.157 0.054 0.068 0.014 0.019 0.016 0.049 0.050 BSC 0.008 0.009 0.004 0.009 0 7 0.228 0.244 0.010 0.019 UC3842B, UC3843B, UC2842B, UC2843B SENSEFET is a trademark of Semiconductor Components Industries, LLC. ON Semiconductor and are trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. PUBLICATION ORDERING INFORMATION NORTH AMERICA Literature Fulfillment: Literature Distribution Center for ON Semiconductor P.O. Box 5163, Denver, Colorado 80217 USA Phone: 303–675–2175 or 800–344–3860 Toll Free USA/Canada Fax: 303–675–2176 or 800–344–3867 Toll Free USA/Canada Email: [email protected] Fax Response Line: 303–675–2167 or 800–344–3810 Toll Free USA/Canada N. American Technical Support: 800–282–9855 Toll Free USA/Canada EUROPE: LDC for ON Semiconductor – European Support German Phone: (+1) 303–308–7140 (Mon–Fri 2:30pm to 7:00pm CET) Email: ONlit–[email protected] French Phone: (+1) 303–308–7141 (Mon–Fri 2:00pm to 7:00pm CET) Email: ONlit–[email protected] English Phone: (+1) 303–308–7142 (Mon–Fri 12:00pm to 5:00pm GMT) Email: [email protected] CENTRAL/SOUTH AMERICA: Spanish Phone: 303–308–7143 (Mon–Fri 8:00am to 5:00pm MST) Email: ONlit–[email protected] Toll–Free from Mexico: Dial 01–800–288–2872 for Access – then Dial 866–297–9322 ASIA/PACIFIC: LDC for ON Semiconductor – Asia Support Phone: 1–303–675–2121 (Tue–Fri 9:00am to 1:00pm, Hong Kong Time) Toll Free from Hong Kong & Singapore: 001–800–4422–3781 Email: ONlit–[email protected] JAPAN: ON Semiconductor, Japan Customer Focus Center 4–32–1 Nishi–Gotanda, Shinagawa–ku, Tokyo, Japan 141–0031 Phone: 81–3–5740–2700 Email: [email protected] ON Semiconductor Website: http://onsemi.com EUROPEAN TOLL–FREE ACCESS*: 00–800–4422–3781 *Available from Germany, France, Italy, UK, Ireland For additional information, please contact your local Sales Representative. http://onsemi.com 20 UC3842B/D