VC VCA822 A8 22 VC A822 SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 Wideband, > 40dB Gain Adjust Range, Linear in V/V VARIABLE GAIN AMPLIFIER FEATURES 1 DESCRIPTION • 150MHz SMALL-SIGNAL BANDWIDTH (G = +10V/V) • 137MHz, 5VPP BANDWIDTH (G = +10V/V) • 0.1dB GAIN FLATNESS to 28MHz • 1700V/µs SLEW RATE • > 40dB GAIN ADJUST RANGE • HIGH GAIN ACCURACY: 20dB ±0.3dB • HIGH OUTPUT CURRENT: ±160mA 23 The VCA822 is a dc-coupled, wideband, linear in V/V, continuously variable, voltage-controlled gain amplifier. It provides a differential input to single-ended conversion with a high-impedance gain control input used to vary the gain down 40dB from the nominal maximum gain set by the gain resistor (RG) and feedback resistor (RF). APPLICATIONS • • • • • • DIFFERENTIAL LINE RECEIVERS DIFFERENTIAL EQUALIZERS PULSE AMPLITUDE COMPENSATION VARIABLE ATTENUATORS VOLTAGE-TUNABLE ACTIVE FILTERS DROP-IN UPGRADE TO LMH6503 VIN1 RF +VIN RG+ RS R1 RL FB RG VOUT VCA822 C1 CL RG- VIN2 -VIN 20W Table 1. VCA822 RELATED PRODUCTS RS DUALS GAIN ADJUST RANGE (dB) VCA810 — 80 2.4 35 — VCA2612 45 1.25 80 3 — VCA2613 45 1 80 0 — VCA2615 52 0.8 50 -3 — VCA2617 48 4.1 50 VCA820 — 40 8.2 150 Figure 1. Differential Equalizer SINGLES 9 Equalized Frequency Response 6 Gain (dB) The VCA822 internal architecture consists of two input buffers and an output current feedback amplifier stage integrated with a multiplier core to provide a complete variable gain amplifier (VGA) system that does not require external buffering. The maximum gain is set externally with two resistors, providing flexibility in designs. The maximum gain is intended to be set between +2V/V and +100V/V. Operating from ±5V supplies, the gain control voltage for the VCA822 adjusts the gain linearly in V/V as the control voltage varies from +1V to –1V. For example, set for a maximum gain of +10V/V, the VCA822 provides 10V/V, at +1V input, to 0.1V/V at –1V input of gain control range. The VCA822 offers excellent gain linearity. For a 20dB maximum gain, and a gain-control input voltage varying between 0V and 1V, the gain does not deviate by more than ±0.3dB (maximum at +25°C). -6 Initial Frequency Response of VCA822 with RC Load -9 INPUT NOISE (nV/√Hz) SIGNAL BANDWIDTH (MHz) VCA821 — 40 7.0 420 -15 VCA822 — 40 8.2 150 -18 VCA824 — 40 7.0 420 -12 -21 RL = 75W CF = 100pF -24 1M 10M 100M 1G Frequency (Hz) Figure 2. Differential Equalization of an RC Load 1 2 3 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. X2Y is a trademark of X2Y Corporation. All other trademarks are the property of their respective owners. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2007, Texas Instruments Incorporated VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. ORDERING INFORMATION (1) SPECIFIED TEMPERATURE RANGE PACKAGE MARKING PRODUCT PACKAGE-LEAD PACKAGE DESIGNATOR VCA822 SO-14 D –40°C to +85°C VCA822ID VCA822 MSOP-10 DGS –40°C to +85°C BOS (1) ORDERING NUMBER TRANSPORT MEDIA, QUANTITY VCA822ID Rail, 50 VCA822IDR Tape and Reel, 2500 VCA822IDGST Tape and Reel, 250 VCA822IDGSR Tape and Reel, 2500 For the most current package and ordering information see the Package Option Addendum at the end of this document, or see the TI web site at www.ti.com. ABSOLUTE MAXIMUM RATINGS (1) Over operating free-air temperature range, unless otherwise noted. VCA822 UNIT ±6.5 V Power supply Internal power dissipation See Thermal Characteristics Input voltage range ±VS V –40 to +125 °C Lead temperature (soldering, 10s) +260 °C Junction temperature (TJ) +150 °C Junction temperature (TJ), maximum continuous operation +140 °C Human body model (HBM) 2000 V Charged device model (CDM) 500 V Machine model (MM) 200 V Storage temperature range ESD ratings (1) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated is not implied. Exposure to absolute-maximum rated conditions for extended periods may affect device reliability. PIN CONFIGURATIONS SO-14 (Top View) MSOP-10 (Top View) +VCC 1 14 +VCC VG 2 13 NC +VIN 3 12 FB +RG 4 11 GND -RG 5 10 VOUT -VIN 6 9 VREF -VCC 7 8 -VCC FB 1 10 GND +VCC 2 9 VOUT VG 3 8 -VCC +VIN 4 7 -VIN +RG 5 6 -RG NC = No Connection 2 Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 ELECTRICAL CHARACTERISTICS: VS = ±5V At AVMAX = +10V/V, RF = 1kΩ, RG = 200Ω, and RL = 100Ω, unless otherwise noted. VCA822 MIN/MAX OVER TEMPERATURE TYP PARAMETER CONDITIONS +25°C +25°C (2) 0°C to 70°C (3) –40°C to +85°C (3) UNITS MIN/ MAX TEST LEVEL (1) AC PERFORMANCE Small-signal bandwidth (SO-14 Package) AVMAX = +2V/V, VO = 1VPP, VG = 1V 168 MHz typ C AVMAX = +10V/V, VO = 1VPP, VG = 1V 150 MHz typ C AVMAX = +100V/V, VO = 1VPP, VG = 1V 118 MHz typ C Large-signal bandwidth AVMAX = +10V/V, VO = 5VPP, VG = 1V 137 MHz typ C Gain control bandwidth VG = 0VDC + 10mVPP 200 MHz min B AVMAX = +10V/V, VO = 1VPP, VG = 1V 28 MHz typ C Slew rate AVMAX = +10V/V, VO = 5V Step, VG = 1V 1700 1500 1500 1450 V/µs min B Rise-and-fall time AVMAX = +10V/V, VO = 5V Step, VG = 1V 2.5 3.1 3.2 3.2 ns max B Settling time to 0.01% AVMAX = +10V/V, VO = 5V Step, VG = 1V 11 ns typ C 2nd-harmonic VO = 2VPP, f = 20MHz, VG = 1V –62 –60 –60 –60 dBc min B 3rd-harmonic VO = 2VPP, f = 20MHz, VG = 1V –68 –66 –66 –66 dBc min B Input voltage noise f > 100kHz, VG = 1V 8.2 nV/√Hz typ C Input current noise f > 100kHz, VG = 1V 2.6 pA/√Hz typ C Bandwidth for 0.1dB flatness 170 170 165 Harmonic distortion GAIN CONTROL Absolute gain error AVMAX = +10V/V, VG = 1V ±0.1 ±0.4 ±0.5 ±0.6 dB max A Gain deviation AVMAX = +10V/V, 0 < VG < 1V ±0.05 ±0.3 ±0.34 ±0.37 dB max A Gain deviation AVMAX = +10V/V, –0.8 < VG < 1V ±1.06 ±1.9 ±2.1 ±2.2 dB max A Relative to maximum gain –26 –24 –24 –23 dB max A VG = 0V 22 30 35 37 µA max A 100 100 nA/°C max B kΩ || pF typ C Gain at VG = –0.9V Gain control bias current Average gain control bias current drift VG = 0V Gain control input impedance 70 || 1 DC PERFORMANCE Input offset voltage Average input offset voltage drift Input bias current Average input bias current drift Input offset current Average input offset current drift AVMAX = +10V/V, VCM = 0V, VG = 0V ±4 ±17 AVMAX = +10V/V, VCM = 0V, VG = 0V AVMAX = +10V/V, VCM = 0V, VG = 0V 19 25 AVMAX = +10V/V, VCM = 0V, VG = 0V AVMAX = +10V/V, VCM = 0V, VG = 0V ±0.5 ±2.5 AVMAX = +10V/V, VCM = 0V, VG = 0V Maximum current through gain resistance (IRG MAX) ±17.8 ±19 mV max A ±30 ±30 µV/°C max B 29 31 µA max A ±90 ±90 nA/°C max B ±3.2 ±3.5 µA max A ±16 ±16 nA/°C max B max B 2.6 2.55 2.55 2.5 mA INPUT Most positive input voltage RL = 100Ω +1.6 +1.6 +1.6 +1.6 V min A Most negative input voltage RL = 100Ω –2.1 –2.1 –2.1 –2.1 V max A VCM = ±0.5V 80 65 60 60 dB min A Common-mode rejection ratio Input impedance (1) (2) (3) Differential 0.5 || 1 MΩ || pF typ C Common-mode 0.5 || 2 MΩ || pF typ C Test levels: (A) 100% tested at +25°C. Over temperature limits set by characterization and simulation. (B) Limits set by characterization and simulation. (C) Typical value only for information. Junction temperature = ambient for +25°C tested specifications. Junction temperature = ambient at low temperature limit; junction temperature = ambient +23°C at high temperature limit for over temperature specifications. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 3 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 ELECTRICAL CHARACTERISTICS: VS = ±5V (continued) At AVMAX = +10V/V, RF = 1kΩ, RG = 200Ω, and RL = 100Ω, unless otherwise noted. VCA822 MIN/MAX OVER TEMPERATURE TYP PARAMETER CONDITIONS +25°C +25°C (2) 0°C to 70°C (3) –40°C to +85°C (3) UNITS MIN/ MAX TEST LEVEL (1) OUTPUT Output voltage swing RL = 1kΩ ±4.0 ±3.8 ±3.75 ±3.7 V min A RL = 100Ω ±3.9 ±3.7 ±3.6 ±3.5 V min A VO = 0V, RL = 5Ω ±160 ±140 ±130 ±130 mA min A AVMAX = +10V/V, f > 100kHz, VG = 1V 0.01 Ω typ C Specified operating voltage ±5 V typ C Minimum operating voltage ±3.5 V typ C Output current Output impedance POWER SUPPLY Maximum operating voltage ±6 ±6 ±6 V max A Maximum quiescent current VG = 0V 36 37 37.5 38 mA max A Minimum quiescent current VG = 0V 36 34.5 34 33.5 mA max A VG = +1V –68 –61 –59 –58 dB min A –40 to +85 °C typ C Power-supply rejection ratio (–PSRR) THERMAL CHARACTERISTICS Specified operating range, D package Thermal resistance, θJA Junction-to-ambient DGS MSOP-10 130 °C/W typ C D SO-14 80 °C/W typ C 4 Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, DC Parameters At TA = +25°C, RL = 100Ω, VG = +1V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. MAXIMUM DIFFERENTIAL INPUT VOLTAGE vs RG MAXIMUM GAIN ADJUST RANGE vs RF 40 IRG MAX = 2.6mA VIN MAX(VPP) = 2 ´ RG ´ IRG MAX (AP) Maximum Gain Adjust Range (dB) Differential Input Voltage (VPP) 10 1 10 100 1k 25 VO = 1VPP 20 VO = 2VPP 15 VO = 4VPP 10 VO = 3VPP 5 100 Figure 3. Figure 4. MAXIMUM GAIN ADJUST RANGE vs PEAK-TO-PEAK OUTPUT VOLTAGE GAIN ERROR BAND vs GAIN CONTROL VOLTAGE 50 RF = 3kW RF = 4kW Gain (V/V) 40 RF = 5kW 30 RF = 500W 20 RF = 1.5kW RF = 2kW 0 0.1 11 10 9 8 7 6 5 Absolute Error Relative Error to Maximum Gain 4 3 2 1 0 RF = 1kW 10 1 -1 -1.2 10 -0.8 0 -0.4 0.4 0.8 Output Voltage (VPP) Control Voltage (V) Figure 5. Figure 6. GAIN ERROR BAND vs GAIN CONTROL VOLTAGE GAIN ERROR BAND vs GAIN CONTROL VOLTAGE 21 Data Equation: y = 20log (4.9619x + 5.0169) 19 Gain (V/V) 18 Data 17 16 Relative Error to Linear Regression 15 14 Linear Regression 13 0 10k Feedback Resistor (W) IRG = 2.6mA AVMAX(V/V) = 2 ´ [RF/VIN(VPP)] ´ 2 ´ IRG (AP) 20 1k Gain Resistor (W) 60 Maximum Gain Adjust Range (dB) 30 0 0.1 Gain (V/V) IRG = 2.6mA AVMAX(V/V) = 2 ´ [RF/VIN(VPP)] ´ 2 ´ IRG (AP) 35 0.2 0.4 0.6 0.8 1.0 24 22 20 18 16 14 12 10 8 6 4 2 0 -2 -4 -6 -0.8 1.2 Relative Error to Linear Regression Linear Regression Data Equation: y = 20log (4.9619x + 5.0169) Data -0.6 -0.4 -0.2 0 0.2 0.4 Control Voltage (V) Control Voltage (V) Figure 7. Figure 8. 0.6 0.8 Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 1.0 5 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, DC and Power-Supply Parameters At TA = +25°C, RL = 100Ω, VG = +1V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. SUPPLY CURRENT vs CONTROL VOLTAGE (AVMAX = +2V/V) RECOMMENDED RF vs AVMAX 40 1500 For > 40dB Gain Adjust Range 39 Quiescent Current (mA) Feedback Resistor (W) 1400 1300 1200 1100 1000 900 NOTE: -3dB bandwidth varies with package type. See the Application section for more details. 800 -IQ 37 +IQ 36 35 34 33 32 -1.0 -0.8 -0.6 -0.4 -0.2 700 1 38 10 100 0.2 0.4 0.6 0.8 Figure 9. Figure 10. SUPPLY CURRENT vs CONTROL VOLTAGE (AVMAX = +10V/V) SUPPLY CURRENT vs CONTROL VOLTAGE (AVMAX = +100V/V) 40 40 39 39 Quiescent Current (mA) Quiescent Current (mA) 0 1.0 Gain Control Voltage (V) AVMAX (V/V) 38 -IQ 37 36 +IQ 35 34 33 38 -IQ 37 36 +IQ 35 34 33 32 -1.0 -0.8 -0.6 -0.4 -0.2 0 0.2 0.4 0.6 0.8 32 -1.0 -0.8 -0.6 -0.4 -0.2 1.0 0 0.2 0.4 Gain Control Voltage (V) Gain Control Voltage (V) Figure 11. Figure 12. 0.6 0.8 1.0 TYPICAL DC DRIFT vs TEMPERATURE 1.0 35 Input Offset Voltage (mV) 0.5 30 0 25 Input Bias Current (IB) Right Scale -0.5 20 -1.0 15 -1.5 10 5 -2.0 10x Input Offset Current (IOS) Right Scale -2.5 0 -3.0 Input Bias and Offset Current (mA) VG = 0V Input Offset Voltage (VOS) Left Scale -5 -50 -25 0 25 50 75 100 125 Temperature (°C) Figure 13. 6 Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +2V/V At TA = +25°C, RL = 100Ω, RF = 1.33kΩ, RG = 1.33kΩ, VG = +1V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. LARGE-SIGNAL FREQUENCY RESPONSE 3 0 0 -3 Normalized Gain (dB) Normalized Gain (dB) SMALL-SIGNAL FREQUENCY RESPONSE 3 VG = 0V -6 -9 VG = 1V -12 AVMAX = 2V/V VIN = 1VPP RL = 100W -15 VO = 1VPP -3 -6 -9 VO = 2VPP -12 VO = 5VPP -15 VO = 7VPP -18 -18 1M 10M 100M 1G 1M Figure 14. Figure 15. SMALL-SIGNAL PULSE RESPONSE LARGE-SIGNAL PULSE RESPONSE VIN = 250mVPP f = 20MHz VIN = 2.5VPP f = 20MHz 3 2 Output Voltage (V) 200 100 0 -100 1 0 -1 -2 -200 -3 -300 Time (10ns/div) Time (10ns/div) Figure 16. Figure 17. COMPOSITE VIDEO dG/dP GAIN FLATNESS, DEVIATION FROM LINEAR PHASE 0.07 0.06 0 0.08 -0.05 0.07 -0.10 -0.10 -0.15 -0.15 -0.20 -0.20 -0.25 -0.25 -0.30 -0.30 -0.35 -0.35 0.02 -0.40 -0.40 0.01 -0.45 -0.45 0 -0.50 0.06 -dG VG = 0V 0.05 -dP VG = 1V 0.04 -dP VG = 0V 0.05 0.04 0.03 0.02 0.01 0 2 3 4 Differential Phase (°) Differential Gain (%) 0.08 0.09 0 AVMAX = +2V/V VG = +1V 0 10 20 30 40 -0.05 50 Deviation from Linear Phase (°) -dG VG = 1V Magnitude (0.05dB/div) 0.09 1 1G 4 300 0.03 100M Frequency (Hz) 400 Output Voltage (mV) 10M Frequency (Hz) -0.50 Frequency (MHz) Number of Video Loads Figure 18. Figure 19. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 7 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +2V/V (continued) At TA = +25°C, RL = 100Ω, RF = 1.33kΩ, RG = 1.33kΩ, VG = +1V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. HARMONIC DISTORTION vs FREQUENCY HARMONIC DISTORTION vs LOAD RESISTANCE -45 -60 VG = +1V AVMAX = +2V/V VO = 2VPP RL = 100W -55 -60 2nd-Harmonic Harmonic Distortion (dBc) Harmonic Distortion (dBc) -50 2nd-Harmonic -65 -70 3rd-Harmonic -75 -80 -85 -65 -70 -75 3rd-Harmonic AVMAX = +2V/V VG = +1V VO = 2VPP f = 20MHz -80 -90 -95 -85 0.1 10 100 100 1k Frequency (MHz) Resistance (W) Figure 20. Figure 21. HARMONIC DISTORTION vs OUTPUT VOLTAGE HARMONIC DISTORTION vs GAIN CONTROL VOLTAGE -40 -50 VG = +1V AVMAX = +2V/V RL = 100W f = 20MHz -55 Harmonic Distortion (dBc) Harmonic Distortion (dBc) 1 -60 2nd-Harmonic -65 -70 3rd-Harmonic VO = 2VPP AVMAX = +2V/V RL = 100W f = 20MHz -45 -50 Maximum Current Through RG Limited -55 2nd-Harmonic -60 -65 -75 -70 -0.6 -80 0.1 1 3rd-Harmonic 10 -0.4 -0.2 0 0.6 0.8 1.0 Figure 22. Figure 23. TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT vs GAIN CONTROL VOLTAGE 40 38 40 Intercept Point (+dBm) Intercept Point (+dBm) 0.4 Gain Control Voltage (V) 45 35 30 25 Constant Input Voltage 36 34 Constant Output Voltage 32 30 28 26 24 22 At 50W Matched Load 20 0 8 0.2 Output Voltage Swing (VPP) 10 20 30 40 50 60 70 fIN = 20MHz At 50W Matched Load 20 -0.6 -0.4 -0.2 0 0.2 0.4 Frequency (MHz) Gain Control Voltage (V) Figure 24. Figure 25. Submit Documentation Feedback 0.6 0.8 1.0 Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +2V/V (continued) At TA = +25°C, RL = 100Ω, RF = 1.33kΩ, RG = 1.33kΩ, VG = +1V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. GAIN vs GAIN CONTROL VOLTAGE GAIN CONTROL FREQUENCY RESPONSE 2.2 2.0 1.8 1.6 3 VG = 0VDC + 10mVPP VIN = 0.5VDC Normalized Gain (dB) 0 Gain (V/V) 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0 -3 -6 -9 -0.2 -1.2 -0.8 0 -0.4 0.4 0.8 -12 1.2 1M 100M Frequency (Hz) Figure 26. Figure 27. GAIN CONTROL PULSE RESPONSE 1G FULLY-ATTENUATED RESPONSE 10 4 0 3 1 0 -1 1.5 1.0 0.5 0 VOUT (V) 2 Differential Input Voltage (VPP) VIN = 1.25VDC VG (V) 10M Gain Control Voltage (V) VG = 1V -10 -20 -30 -40 VG = -1V -50 -60 -70 -80 -0.5 -90 -1.0 -100 VO = 2VPP 1M Time (10ns/div) 10M 100M 1G Frequency (Hz) Figure 28. Figure 29. GROUP DELAY vs GAIN CONTROL VOLTAGE GROUP DELAY vs FREQUENCY 1.8 1.6 1MHz 1.6 1.4 10MHz 1.2 Group Delay (ns) Group Delay (ns) 1.4 1.2 20MHz 1.0 0.8 0.6 1.0 0.8 0.6 0.4 0.4 VG = +1V VO = 1VPP 0.2 0.2 0 -1.0 -0.8 -0.6 -0.4 -0.2 0 0 0.2 0.4 0.6 0.8 1.0 0 20 40 60 Gain Control Voltage (V) Frequency (MHz) Figure 30. Figure 31. 80 Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 100 9 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +2V/V (continued) At TA = +25°C, RL = 100Ω, RF = 1.33kΩ, RG = 1.33kΩ, VG = +1V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. RECOMMENDED RS vs CAPACITIVE LOAD FREQUENCY RESPONSE vs CAPACITIVE LOAD Normalized Gain to Capacitive Load (dB) RS (W) 100 10 0.1dB Flatness Targeted 0 1 10 100 9 CL = 47pF 0 CL = 100pF -3 RF -6 VIN +VIN RS 1.33kW VOUT VCA822 20W -9 (1) 1kW -VIN NOTE: (1) 1kW is optional. -12 1M 1k 10M 100M Frequency (Hz) Figure 32. Figure 33. OUTPUT VOLTAGE NOISE DENSITY 1G INPUT CURRENT NOISE DENSITY 10 Input Voltage Noise Density (pA/ÖHz) Output Voltage Noise Density (nV/ÖHz) CL = 10pF 3 Capacitive Load (pF) 1000 VG = +1V VG = 0V 100 VG = -1V 1 10 100 1k 10k 100k 1M 10M 100 1k 10k 100k 1M 10M Frequency (Hz) Frequency (Hz) Figure 34. 10 CL = 22pF VO = 0.5VPP 6 Figure 35. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +10V/V At TA = +25°C, RL = 100Ω, RF = 1kΩ, RG = 200Ω, VG = +1V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. LARGE-SIGNAL FREQUENCY RESPONSE 3 0 0 Normalized Gain (dB) Normalized Gain (dB) SMALL-SIGNAL FREQUENCY RESPONSE 3 -3 VG = 1V -6 -9 -12 AVMAX = 10V/V VIN = 200mVPP RL = 100W -15 VO = 2VPP -6 -9 VO = 5VPP -12 VO = 7VPP -15 VG = 0V -18 -18 1M -3 10M 100M 0 1G 50 150 Figure 36. Figure 37. 350 400 LARGE-SIGNAL PULSE RESPONSE VIN = 50mVPP f = 20MHz VIN = 0.5VPP f = 20MHz Output Voltage (V) 2 100 0 -100 -200 1 0 -1 -2 -300 -3 Time (10ns/div) Time (10ns/div) Figure 38. Figure 39. GAIN FLATNESS, DEVIATION FROM LINEAR PHASE OUTPUT VOLTAGE NOISE DENSITY 0.05 0 -0.05 -0.05 -0.10 -0.10 -0.15 -0.15 -0.20 -0.20 -0.25 -0.25 VG = +1V AVMAX = +10V/V -0.30 -0.35 -0.35 10 20 30 Frequency (MHz) 40 50 Deviation From Linear Phase (°) 0 1000 Output Voltage Noise Density (nV/ÖHz) 0.05 Magnitude (0.05dB/div) 300 3 200 0 250 Frequency (Hz) SMALL-SIGNAL PULSE RESPONSE -0.30 200 Frequency (MHz) 300 Output Voltage (mV) 100 VG = +1V VG = 0V 100 VG = -1V 10 100 1k 10k 100k 1M 10M Frequency (Hz) Figure 40. Figure 41. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 11 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +10V/V (continued) At TA = +25°C, RL = 100Ω, RF = 1kΩ, RG = 200Ω, VG = +1V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. HARMONIC DISTORTION vs FREQUENCY -45 VG = +1V AVMAX = +10V/V VO = 2VPP RL = 100W -55 2nd-Harmonic -60 Harmonic Distortion (dBc) -50 Gain (dB) HARMONIC DISTORTION vs LOAD RESISTANCE -60 2nd-Harmonic -65 -70 3rd-Harmonic -75 -80 -70 3rd-Harmonic -75 -80 -85 VG = +1V AVMAX = +10V/V VO = 2VPP f = 20MHz -90 -85 0.1 1 10 100 100 Resistance (W) Figure 42. Figure 43. HARMONIC DISTORTION vs OUTPUT VOLTAGE HARMONIC DISTORTION vs GAIN CONTROL VOLTAGE -45 Harmonic Distortion (dBc) -60 2nd-Harmonic -65 -70 3rd-Harmonic VG = +1V AVMAX = +10V/V RL = 100W f = 20MHz -75 VO = 2VPP AVMAX = +10V/V RL = 100W f = 20MHz -50 -55 Max Current Through RG Limited -60 2nd-Harmonic -65 3rd-Harmonic -70 -0.6 -80 0.1 1 10 -0.2 0 0.2 0.4 0.6 0.8 1.0 Gain Control Voltage (V) Figure 44. Figure 45. TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT vs GAIN CONTROL VOLTAGE (fIN = 20MHz) 40 38 Intercept Point (+dBm) 40 Intercept Point (+dBm) -0.4 Output Voltage Swing (VPP) 45 35 30 25 Constant Output Voltage 36 34 32 Constant Input Voltage 30 28 26 24 22 At 50W Matched Load 20 5 12 1k Frequency (MHz) -55 Harmonic Distortion (dBc) -65 10 15 20 25 30 35 40 45 50 55 60 65 70 At 50W Matched Load 20 -0.6 -0.4 -0.2 0 0.2 0.4 Frequency (MHz) Gain Control Voltage (V) Figure 46. Figure 47. Submit Documentation Feedback 0.6 0.8 1.0 Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +10V/V (continued) At TA = +25°C, RL = 100Ω, RF = 1kΩ, RG = 200Ω, VG = +1V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. GAIN CONTROL FREQUENCY RESPONSE 6 3 Normalized Gain (dB) Gain (V/V) GAIN vs GAIN CONTROL VOLTAGE 11 10 9 8 7 6 5 4 3 2 1 0 0 -3 -6 -9 -12 -15 -1 -1.2 -18 -0.8 0 -0.4 0.4 0.8 1.2 1M 10M 100M Gain Control Voltage (V) Frequency (Hz) Figure 48. Figure 49. GAIN CONTROL PULSE RESPONSE 5 3 4 1 VOUT (V) 2 100W Load Line 3 0 -1 1.5 1G OUTPUT VOLTAGE AND CURRENT LIMITATIONS 4 Output Voltage (V) VIN = 0.25VDC 1.0 VG (V) VG = 0VDC + 10mVPP VIN = 0.1VDC 0.5 2 1W Internal Power Dissipation 25W Load Line 1 0 50W Load Line -1 1W Internal Power Dissipation -2 0 -3 -0.5 -4 -5 -300 -1.0 Time (10ns/div) -200 -100 0 100 200 300 Output Current (mA) Figure 50. Figure 51. IRG LIMITED OVERDRIVE RECOVERY 2.0 1.5 VG = 1V 8 AVMAX = +10V/V VG = -0.3V Input Voltage Left Scale 4 1.0 VIN (V) 0.5 Input-Referred 0 0 -0.5 -1.0 VG = -1V VO = 2VPP Output Voltage Right Scale 10M 100M -4 -1.5 -8 -2.0 1M VOUT (V) Gain (dB) FULLY-ATTENUATED RESPONSE 30 20 10 0 -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 1G Time (40ns/div) Frequency (Hz) Figure 52. Figure 53. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 13 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +10V/V (continued) At TA = +25°C, RL = 100Ω, RF = 1kΩ, RG = 200Ω, VG = +1V, and VIN = single-ended input on +VIN with –VIN at ground, unless otherwise noted. OUTPUT LIMITED OVERDRIVE RECOVERY 2.0 1.5 AVMAX = +10V/V VG = 1.0V Output Voltage Right Scale GROUP DELAY vs GAIN CONTROL VOLTAGE 8 1.85 6 1.80 0.5 2 0 -0.5 0 Input Voltage Left Scale -2 Group Delay (ns) 4 VOUT (V) Input Voltage (V) 1MHz 1.0 1.75 10MHz 1.70 1.65 1.60 -1.0 -4 -1.5 -6 1.55 -8 1.50 -1.0 -0.8 -0.6 -0.4 -0.2 -2.0 20MHz Time (40ns/div) 0 0.2 0.4 0.6 0.8 1.0 Gain Control Voltage (V) Figure 54. Figure 55. GROUP DELAY vs FREQUENCY 1.9 1.8 Group Delay (ns) 1.7 1.6 1.5 1.4 1.3 1.2 VG = +1V VO = 1VPP 1.1 1.0 0 20 40 60 80 100 Frequency (MHz) Figure 56. 14 Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +100V/V At TA = +25°C, RL = 100Ω, RF = 845Ω, RG = 16.9Ω, VG = +1V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. SMALL-SIGNAL FREQUENCY RESPONSE LARGE-SIGNAL FREQUENCY RESPONSE 3 3 VG = 1V 0 -3 -3 VG = 0V Gain (dB) Normalized Gain (dB) 0 -6 -9 VO = 2VPP -6 -9 VO = 7VPP -12 -12 AVMAX = 100V/V VIN = 20mVPP RL = 100W -15 -18 1 -15 VO = 5VPP -18 10 100 0 500 100 Figure 57. Figure 58. 250 300 LARGE-SIGNAL PULSE RESPONSE 3 VIN = 50mVPP f = 20MHz VIN = 5mVPP f = 20MHz 200 Output Voltage (V) 2 100 0 -100 -200 1 0 -1 -2 -300 -3 Time (10ns/div) Time (10ns/div) Figure 59. Figure 60. GAIN FLATNESS OUTPUT VOLTAGE NOISE DENSITY 0.1 0.05 0 0 -0.1 -0.05 -0.2 -0.10 -0.3 -0.15 -0.4 -0.20 -0.5 -0.25 -0.6 -0.30 -0.7 10 20 30 40 50 1000 Deviation from Linear Phase (°) VG = +1V AVMAX = +100V/V Output Voltage Noise Density (nV/ÖHz) 0.10 Magnitude (0.05dV/div) 200 Frequency (MHz) SMALL-SIGNAL PULSE RESPONSE 0 150 Frequency (MHz) 300 Output Voltage (mV) 50 VG = +1V VG = 0V 100 VG = -1V 10 100 Frequency (MHz) 1k 10k 100k 1M 10M Frequency (Hz) Figure 61. Figure 62. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 15 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +100V/V (continued) At TA = +25°C, RL = 100Ω, RF = 845Ω, RG = 16.9Ω, VG = +1V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. HARMONIC DISTORTION vs FREQUENCY -35 VG = +1V AVMAX = +100V/V VO = 2VPP RL = 100W -45 -50 -55 2nd-Harmonic -45 Harmonic Distortion (dBc) -40 Harmonic Distortion (dBc) HARMONIC DISTORTION vs LOAD RESISTANCE -40 2nd-Harmonic -60 -65 -70 3rd-Harmonic -75 -50 -55 -65 -70 -75 -80 -85 -80 3rd-Harmonic -60 VG = +1V AVMAX = +100V/V VO = 2VPP f = 20MHz -90 0.1 1 10 100 100 Resistance (W) Figure 63. Figure 64. HARMONIC DISTORTION vs OUTPUT VOLTAGE HARMONIC DISTORTION vs GAIN CONTROL VOLTAGE -30 -40 2nd-Harmonic 3rd-Harmonic Harmonic Distortion (dBc) Harmonic Distortion (dBc) 1k Frequency (MHz) -45 -50 3rd-Harmonic -55 VG = 1VPP AVMAX = +100V/V RL = 100W f = 20MHz -60 1 -50 Maximum Current Through RG Limited -60 -70 10 VO = 2VPP AVMAX = +100V/V RL = 100W f = 20MHz 2nd-Harmonic -80 -0.6 -65 0.1 -40 -0.4 -0.2 0 0.2 0.4 0.6 0.8 1.0 Output Voltage Swing (VPP) Gain Control Voltage (V) Figure 65. Figure 66. TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT TWO-TONE, 3RD-ORDER INTERMODULATION INTERCEPT vs GAIN CONTROL VOLTAGE (fIN = 20MHz) 33 31 31 29 29 Intercept Point (+dBm) Intercept Point (+dBm) Constant Input Voltage 27 25 23 21 19 25 Constant Output Voltage 23 21 19 17 17 At 50W Matched Load 15 5 16 27 10 15 20 25 30 35 40 45 50 55 60 65 70 At 50W Matched Load 15 -0.6 -0.4 -0.2 0 0.2 0.4 Frequency (MHz) Gain Control Voltage (V) Figure 67. Figure 68. Submit Documentation Feedback 0.6 0.8 1.0 Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +100V/V (continued) At TA = +25°C, RL = 100Ω, RF = 845Ω, RG = 16.9Ω, VG = +1V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. GAIN vs GAIN CONTROL VOLTAGE GAIN CONTROL FREQUENCY RESPONSE 3 VG = 0VDC + 10mVPP VIN = 10mVDC 100 90 80 70 60 50 40 30 20 10 0 0 Normalized Gain (dB) Gain (V/V) 110 Feedthrough -3 -6 -9 -10 -1.2 -12 -0.8 -0.4 0 0.4 0.8 1.2 1M 10M Frequency (Hz) Figure 69. Figure 70. GAIN CONTROL PULSE RESPONSE 50 3 40 1 VOUT (V) 2 2G VG = 1V 30 0 -1 1.5 1G FULLY-ATTENUATED RESPONSE 4 Normalized Gain (dB) VIN = 25mVDC 1.0 VG (V) 100M Gain Control Voltage (V) 0.5 20 10 0 -10 -20 -30 0 -40 -0.5 -50 VG = -1V VO = 2VPP -60 -1.0 1M Time (10ns/div) 10M 100M 1G Frequency (Hz) Figure 71. Figure 72. IRG LIMITED OVERDRIVE RECOVERY 6 0.15 0.4 4 0.10 4 0.2 2 0.05 2 0 0 0 0 AVMAX = +100V/V VG = -0.3V Input Voltage Left Scale -0.4 -2 Output Voltage Right Scale -0.6 -0.8 -4 -0.05 -0.10 -6 -0.15 -8 -0.20 8 AVMAX = +100V/V VG = 1.0V Output Voltage Right Scale 6 -8 Input Voltage Left Scale -6 Output Voltage (V) -0.2 Output Voltage (V) 0.20 0.6 Input Voltage (V) OUTPUT LIMITED OVERDRIVE RECOVERY 8 Input Voltage (V) 0.8 -4 -2 Time (40ns/div) Time (40ns/div) Figure 73. Figure 74. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 17 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 TYPICAL CHARACTERISTICS: VS = ±5V, AVMAX = +100V/V (continued) At TA = +25°C, RL = 100Ω, RF = 845Ω, RG = 16.9Ω, VG = +1V, VIN = single-ended input on +VIN with –VIN at ground, and SO-14 package, unless otherwise noted. GROUP DELAY vs GAIN CONTROL VOLTAGE GROUP DELAY vs FREQUENCY 3.0 3.5 20MHz 3.0 Group Delay (ns) Group Delay (ns) 2.5 2.0 10MHz 1MHz 1.5 1.0 0.5 2.0 1.5 1.0 VG = +1V VO = 1VPP 0.5 0 -1.0 -0.8 -0.6 -0.4 -0.2 18 2.5 0 0 0.2 0.4 0.6 0.8 1.0 0 20 40 60 Gain Control Voltage (V) Frequency (MHz) Figure 75. Figure 76. Submit Documentation Feedback 80 100 Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 APPLICATION INFORMATION For test purposes, the input impedance is set to 50Ω with a resistor to ground and the output impedance is set to 50Ω with a series output resistor. Voltage swings reported in the Electrical Characteristics table are taken directly at the input and output pins, while output power (dBm) is at the matched 50Ω load. For the circuit in Figure 77, the total effective load is 100Ω 1kΩ. Note that for the SO-14 package, there is a ground pin, GND (pin 11). For the SO-14 package, this pin must be connected to ground through a 20Ω resistor in order to avoid possible oscillations of the output stage. In the MSOP-10 package, this pin is internally connected and does not require such precaution. An X2Y™ capacitor has been used for power-supply bypassing. The combination of low inductance, high resonance frequency, and integration of three capacitors in one package (two capacitors to ground and one across the supplies) of this capacitor enables to achieve the low second-harmonic distortion reported in the Electrical Characteristics table. More information on how the VCA822 operates can be found in the Operating Suggestions section. WIDEBAND VARIABLE GAIN AMPLIFIER OPERATION The VCA822 provides an exceptional combination of high output power capability with a wideband, greater than 40dB gain adjust range, linear in V/V variable gain amplifier. The VCA822 input stage places the transconductance element between two input buffers, using the output currents as the forward signal. As the differential input voltage rises, a signal current is generated through the gain element. This current is then mirrored and gained by a factor of two before reaching the multiplier. The other input of the multiplier is the voltage gain control pin, VG. Depending on the voltage present on VG, up to two times the gain current is provided to the transimpedance output stage. The transimpedance output stage is a current-feedback amplifier providing high output current capability and high slew rate, 1700V/µs. This exceptional full-power performance comes at the price of a relatively high quiescent current (36mA), but a low input voltage noise for this type of architecture (8.2nV/√Hz). Figure 77 shows the dc-coupled, gain of +10V/V, dual power-supply circuit used as the basis of the ±5V Electrical Characteristics and Typical Characteristics. +5V 0.1mF X2Yâ Capacitor -5V + 2.2mF + 2.2mF VG +VIN VIN 20W x1 RG+ RG 200W FB IRG RF 1kW x2 RG- VOUT VOUT x1 20W -VIN VREF VCA822 20W Figure 77. DC-Coupled, AVMAX = +10V/V, Bipolar Supply Specification and Test Circuit Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 19 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 FOUR-QUADRANT MULTIPLIER DIFFERENCE AMPLIFIER A four-quadrant multiplier can easily be implemented using the VCA822. By placing a resistor between FB and VIN, the transfer function depends upon both VIN and VG, as shown in Equation 1. RF RF RF VOUT = ´ VG ´ VIN + ´ VIN R1 RG RG Because both inputs of the VCA822 are high-impedance, a difference amplifier can be implemented without any major problem. This implementation is shown in Figure 80. This circuit provides excellent common-mode rejection ratio (CMRR) as long as the input is within the CMRR range of –2.1V to +1.6V. Note that this circuit does not make use of the gain control pin, VG. Also, it is recommended to choose RS such that the pole formed by RS and the parasitic input capacitance does not limit the bandwidth of the circuit. The common-mode rejection ratio for this circuit implemented in a gain of +10V/V for VG = +1V is shown in Figure 81. Note that because the gain control voltage is fixed and is normally set to +1V, the feedback element can be reduced in order to increase the bandwidth. When reducing the feedback element make sure that the VCA822 is not limited by common-mode input voltage, the current flowing through RG, or any other limitation described in this data sheet. (1) Setting R1 to equal RG, the term that depends only on VIN drops out of the equation, leaving only the term that depends on both VG and VIN. VOUT then follows Equation 2. RF VOUT = ´ VIN ´ VG RG (2) R1 VG RF VIN +VIN RG+ FB VCA822 R2 RS Source Impedance RG RF VIN+ RG-VIN +VIN RG+ RS RG 20W R3 FB VCA822 RG-VIN VIN- 20W RS Figure 78. Four-Quadrant Multiplier Circuit 1.5 fIN = 1MHz fVG = 0.1MHz Amplitude (V) 1.0 0.5 0 -0.5 VIN VOUT -1.0 Figure 80. Difference Amplifier 95 Common-Mode Rejection Ratio (dB) The behavior of this circuit is illustrated in Figure 79. Keeping the input amplitude of a 1MHz signal constant and varying the VG voltage (100kHz, 2VPP) gives the modulated output voltage shown in Figure 79. 90 85 80 75 70 65 60 55 50 45 Input-Referred 40 100k 1M 10M 100M Frequency (Hz) VG -1.5 0 1 2 3 4 5 6 7 8 9 10 Figure 81. Common-Mode Rejection Ratio Time (ms) Figure 79. Modulated Output Signal of the 4-Quadrant Multiplexer Circuit 20 Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 DIFFERENTIAL EQUALIZER 9 Equalized Frequency Response 6 3 0 Gain (dB) If the application requires frequency shaping (the transition from one gain to another), the VCA822 can be used advantageously because its architecture allows the application to isolate the input from the gain setting elements. Figure 82 shows an implementation of such a configuration. The transfer function is shown in Equation 3. RF 1 + sRGC1 ´ G=2´ RG 1 + sR1C1 (3) -3 -6 Initial Frequency Response of VCA822 with RC Load -9 -12 -15 -18 -21 -24 1M +VIN RG+ RS R1 1G VCA822 C1 DIFFERENTIAL CABLE EQUALIZER RGVIN2 100M Figure 83. Differential Equalization of an RC Load FB RG 10M Frequency (Hz) -VIN 20W RS Figure 82. Differential Equalizer This transfer function has one pole, P1 (located at RGC1), and one zero, Z1 (located at R1C1). When equalizing an RC load, RL and CL, compensate the pole added by the load located at RLCL with the zero Z1. Knowing RL, CL, and RG allows the user to select C1 as a first step and then calculate R1. Using RL = 75Ω, CL = 100pF and wanting the VCA822 to operate at a gain of +2V/V, which gives RF = RG = 1.33kΩ, allows the user to select C1 = 5pF to ensure a positive value for the resistor R1. With all these values known, R1 can be calculated to be 170Ω. The frequency response for both the initial, unequalized frequency response and the resulting equalized frequency response are shown in Figure 83. A differential cable equalizer can easily be implemented using the VCA822. An example of a cable equalization for 100 feet of Belden Cable 1694F is illustrated in Figure 85, with the result for this implementation shown in Figure 84. This implementation has a maximum error of 0.2dB from dc to 40MHz. 2.0 Cable Attenuations 1694F Cable Attenuation (dB) Equalizer Gain (dB) VIN1 RF 1.5 1.0 VCA822 with Equalization 0.5 0 -0.5 -1.0 1 10 100 Frequency (MHz) Figure 84. Cable Attenuation versus Equalizer Gain Note that this implementation shows the cable attenuation side-by-side with the equalization in the same plot. For a given frequency, the equalization function realized with the VCA822 matches the cable attenuation. The circuit in Figure 85 is a driver circuit. To implement a receiver circuit, the signal is received differentially between the +VIN and –VIN inputs. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 21 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 VIN R2 1.33kW +VIN R8 50W RG+ R18 40kW R17 17.5kW R21 8.7kW R9 1.27kW VCA822 C7 100nF RG- FB VREF GND VG -VIN C6 120nF R1 20W VOUT R10 75W VOUT 75W Load R5 50W C5 1.42pF VG = +1VDC C9 10mF Figure 85. Differential Cable Equalizer VOLTAGE-CONTROLLED LOW-PASS FILTER In the circuit of Figure 86, the VCA822 serves as the variable-gain element of a voltage-controlled low-pass filter. This section discusses how this implementation expands the circuit voltage swing capability over that normally achieved with the equivalent multiplier implementation. The circuit control voltage, VG, is calculated as according to the simplified relationship in Equation 4: VOUT R2 1 =´ R2 C VIN R1 1+s (4) G R2 332W 24pF C R1 332W RF 1kW VIN 24pF +VIN RG+ OPA690 RG 200W FB VCA822 Out VOUT RG-VIN 20W 50W VG Figure 86. Voltage-Control Low-Pass Filter The response control results from amplification of the feedback voltage applied to R2. First, consider the case where the VCA822 produces G = 1V/V. Then 22 this circuit performs as if the amplifier were replaced by a short circuit. Visually replacing the amplifier by a short leaves a simple voltage-feedback amplifier with a feedback resistor bypassed by a capacitor. Replacing this gain with a variable gain, G, the pole can be written as shown in Equation 5: G f8 = 2pR2C (5) Because the VCA822 is most linear in the midrange, the median of the adjustable pole should be set at VG = 0V (see Figure 26, Figure 46, Figure 67, and Equation 6). Selecting R1 = R2 = 332Ω, and targeting a median frequency of 10MHz, the capacitance (C) is 24pF. Because the OPA690 was selected for the circuit of Figure 86, and in order to limit peaking in the OPA690 frequency response, a capacitor equal to C was added on the inverting mode to ground. This architecture has the effect of setting the high-frequency noise gain of the OPA690 to +2V/V, ensuring stability and providing flat frequency response. -0.8V £ VG £ 0.8V (6) Once the median frequency is set, the maximum and minimum frequencies can be determined by using VG = –0.8V and VG = +0.8V in the gain equation of Equation 7. Note that this is a first-order analysis and does not take into consideration the open-loop gain limitation of the OPA690. RF VG + 1 G=2´ ´ RG 2 (7) Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 With the components shown, the circuit provides a linear variation of the low-pass cutoff from 2MHz to 20MHz, using –1V ≤ VG ≤ +1V. Practical evaluation shows that this circuit works from 8MHz to 16MHz with –0.8V < VG < +0.8V, as shown in Figure 87. 3 VG = +0.8V 0 -3 VG = +0.5V Gain (dB) -6 -9 VG = 0V -12 VG = -0.5V -15 -18 VG = -0.8V -21 VOUT = 1VPP 25 50 75 100 125 150 175 200 Frequency (MHz) Figure 87. VCA822 as a Voltage-Control, Low-Pass Filter DESIGN-IN TOOLS DEMONSTRATION BOARDS Two printed circuit boards (PCBs) are available to assist in the initial evaluation of circuit performance using the VCA822 in its two package options. Both of these are offered free of charge as unpopulated PCBs, delivered with a user's guide. The summary information for these fixtures is shown in Table 2. Table 2. EVM Ordering Information PRODUCT PACKAGE Computer simulation of circuit performance using SPICE is often useful when analyzing the performance of analog circuits and systems. This principle is particularly true for video and RF amplifier circuits where parasitic capacitance and inductance can play a major role in circuit performance. A SPICE model for the VCA822 is available through the TI web page. The applications group is also available for design assistance. The models available from TI predict typical small-signal ac performance, transient steps, dc performance, and noise under a wide variety of operating conditions. The models include the noise terms found in the electrical specifications of the relevant product data sheet. OPERATING SUGGESTIONS -24 0 MACROMODELS AND APPLICATIONS SUPPORT BOARD PART NUMBER LITERATURE REQUEST NUMBER VCA822ID SO-14 DEM-VCA-SO-1B SBOU050 VCA822IDGS MSOP-10 DEM-VCA-MSOP-1A SBOU051 The demonstration fixtures can be requested at the Texas Instruments web site (www.ti.com) through the VCA822 product folder. Operating the VCA822 optimally for a specific application requires trade-offs between bandwidth, input dynamic range and the maximum input voltage, the maximum gain of operation and gain, output dynamic range and the maximum input voltage, the package used, loading, and layout and bypass recommendations. The Typical Characteristics have been defined to cover as much ground as possible to describe the VCA822 operation. There are four sections in the Typical Characteristics: • VS = ±5V DC Parameters and VS = ±5V DC and Power-Supply Parameters, which include dc operation and the intrinsic limitation of a VCA822 design • VS = ±5V, AVMAX = +2V/V Gain of +2V/V Operation • VS = ±5V, AVMAX = +10V/V Gain of +10V/V Operation • VS = ±5V, AVMAX = +100V/V Gain of +100V/V Operation Where the Typical Characteristics describe the actual performance that can be achieved by using the amplifier properly, the following sections describe in detail the trade-offs needed to achieve this level of performance. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 23 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 PACKAGE CONSIDERATIONS 3 Figure 88 shows a test gain circuit for the VCA822. Table 3 lists the recommended configuration for the SO-14 and MSOP-10 package. 0 Normalized Gain (dB) The VCA822 is available in both SO-14 and MSOP-10 packages. Each package has, for the different gains used in the typical characteristics, different values of RF and RG in order to achieve the same performance detailed in the Electrical Characteristics table. AVMAX = 2V/V -3 AVMAX = 5V/V -6 AVMAX = 10V/V AVMAX = 20V/V -9 AVMAX = 50V/V AVMAX = 100V/V -12 0 +VIN VIN R1 50W Source 100 RG+ VOUT R3 200 Figure 89. SO-14 Recommended RF and RG versus AVMAX 50W RG- 150 Frequency (MHz) RG R2 50 RF 50W Load 3 -VIN 50W Normalized Gain (dB) 0 VG Figure 88. Test Circuit Table 3. SO-14 and MSOP-10 RF and RG Configurations G=2 G = 10 G = 100 RF 1.33kΩ 1kΩ 845Ω RG 1.33kΩ 200Ω 16.9Ω There are no differences between the packages in the recommended values for the gain and feedback resistors. However, the bandwidth for the VCA822IDGS (MSOP-10 package) is lower than the bandwidth for the VCA822ID (SO-14 package). This difference is true for all gains, but especially true for gains greater than 5V/V, as can be seen in Figure 89 and Figure 90. Note that the scale must be changed to a linear scale to view the details. 24 AVMAX = 10V/V AVMAX = 2V/V -3 AVMAX = 20V/V -6 AVMAX = 50V/V -9 AVMAX = 100V/V AVMAX = 5V/V -12 0 50 100 150 200 Frequency (MHz) Figure 90. MSOP-10 Recommended RF and RG versus AVMAX MAXIMUM GAIN OF OPERATION This section describes the use of the VCA822 in a fixed-gain application in which the VG control pin is set at VG = +1V. The tradeoffs described here are with bandwidth, gain, and output voltage range. In the case of an application that does not make use of the VGAIN, but requires some other characteristic of the VCA822, the RG resistor must be set such that the maximum current flowing through the resistance IRG is less than ±2.6mA typical, or 5.2mAPP as defined in the Electrical Characteristics table, and must follow Equation 8. VOUT IRG = AVMAX ´ RG (8) Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 As illustrated in Equation 8, once the output dynamic range and maximum gain are defined, the gain resistor is set. This gain setting in turn affects the bandwidth, because in order to achieve the gain (and with a set gain element), the feedback element of the output stage amplifier is set as well. Keeping in mind that the output amplifier of the VCA822 is a current-feedback amplifier, the larger the feedback element, the lower the bandwidth as the feedback resistor is the compensation element. INPUT VOLTAGE DYNAMIC RANGE Limiting the discussion to the input voltage only and ignoring the output voltage and gain, Figure 3 illustrates the tradeoff between the input voltage and the current flowing through the gain resistor. As such, for unity-gain or under-attenuated conditions, the input voltage must be limited to the CMIR of ±1.6V (3.2VPP) and the current (IRQ) must flow through the gain resistor, ±2.6mA (5.2mAPP). This configuration sets a minimum value for RE such that the gain resistor has to be greater than Equation 10. 3.2VPP RGMIN = = 615.4W 5.2mAPP (10) OUTPUT CURRENT AND VOLTAGE The VCA822 provides output voltage and current capabilities that are unsurpassed in a low-cost monolithic VCA. Under no-load conditions at +25°C, the output voltage typically swings closer than 1V to either supply rails; the +25°C swing limit is within 1.2V of either rails. Into a 15Ω load (the minimum tested load), it is tested to deliver more than ±160mA. The specifications described above, though familiar in the industry, consider voltage and current limits separately. In many applications, it is the voltage × current, or V-I product, that is more relevant to circuit operation. Refer to the Output Voltage and Current Limitations plot (Figure 51) in the Typical Characteristics. The X- and Y-axes of this graph show the zero-voltage output current limit and the zero-current output voltage limit, respectively. The four quadrants give a more detailed view of the VCA822 output drive capabilities, noting that the graph is bounded by a Safe Operating Area of 1W maximum internal power dissipation. Superimposing resistor load lines onto the plot shows that the VCA822 can drive ±2.5V into 25Ω or ±3.5V into 50Ω without exceeding the output capabilities or the 1W dissipation limit. A 100Ω load line (the standard test circuit load) shows the full ±3.9V output swing capability, as shown in the Typical Characteristics. The minimum specified output voltage and current over-temperature are set by worst-case simulations at the cold temperature extreme. Only at cold startup do the output current and voltage decrease to the numbers shown in the Electrical Characteristic tables. As the output transistors deliver power, the respective junction temperatures increase, increasing the available output voltage swing, and increasing the available output current. In steady-state operation, the available output voltage and current is always greater than that temperature shown in the over-temperature specifications because the output stage junction temperatures are higher than the specified operating ambient. The VCA822 has a input dynamic range limited to +1.6V and –2.1V. Increasing the input voltage dynamic range can be done by using an attenuator network on the input. If the VCA822 is trying to regulate the amplitude at the output, such as in an AGC application, the input voltage dynamic range is directly proportional to Equation 9. VIN(PP) = RG ´ IRG(PP) (9) Values lower than 615.4Ω are gain elements that result in reduced input range, as the dynamic input range is limited by the current flowing through the gain resistor RG (IRG). If the IRG current is limiting the performance of the circuit, the input stage of the VCA822 goes into overdrive, resulting in limited output voltage range. Such IRG-limited overdrive conditions are shown in Figure 53 for the gain of +10V/V and Figure 73 for the +100V/V gain. OUTPUT VOLTAGE DYNAMIC RANGE With its large output current capability and its wide output voltage swing of ±3.9V typical on 100Ω load, it is easy to forget other types of limitations that the VCA822 can encounter. For these limitations, careful analysis must be done to avoid input stage limitation, either voltage or IRG current; also, consider the gain limitation, as the control pin VG varies, affecting other aspects of the circuit. BANDWIDTH The output stage of the VCA822 is a wideband current-feedback amplifier. As such, the feedback resistance is the compensation of the last stage. Reducing the feedback element and maintaining the gain constant limits the useful range of IRG, and therefore reducing the gain adjust range. For a given gain, reducing the gain element limits the maximum achievable output voltage swing. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 25 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 OFFSET ADJUSTMENT As a result of the internal architecture used on the VCA822, the output offset voltage originates from the output stage and from the input stage and multiplier core. Figure 92 shows how to compensate both sources of the output offset voltage. Use this procedure to compensate the output offset voltage: starting with the output stage compensation, set VG = –1V to eliminate all offset contribution of the input stage and multiplier core. Adjust the output stage offset compensation potentiometer. Finally, set VG = +1V to the maximum gain and adjust the input stage and multiplier core potentiometer. This procedure effectively eliminates all offset contribution at the maximum gain. Because adjusting the gain modifies the contribution of the input stage and the multiplier core, some residual output offset voltage remains. This model is formulated in Equation 11 and Figure 91. 2 ´ (RS ´ in)2 + en2 + 2 ´ 4kTRS eO = AVMAX ´ (11) A more complete model is shown in Figure 93. For additional information on this model and the actual modeled noise terms, please contact the High-Speed Product Application Support team at www.ti.com. RF in RS +VIN RG+ eO RG * FB VCA822 eO RG-VIN 4kTRS in RS * 4kTRS NOTE: RF and RG are noiseless. NOISE The VCA822 offers 8.2nV/√Hz input-referred voltage noise density at a gain of +10V/V and 1.8 pA/√Hz input-referred current noise density. The input-referred voltage noise density considers that all noise terms, except the input current noise but including the thermal noise of both the feedback resistor and the gain resistor, are expressed as one term. Figure 91. Simple Noise Model +5V Output Stage Offset Compensation Circuit 10kW 4kW 0.1mF -5V RF VIN +VIN RG+ 50W RG FB VOUT VCA822 RG-VIN +5V 1kW 50W 10kW 0.1mF -5V Input Stage and Multiplexer Core Offset Compensation Circuit Figure 92. Adjusting the Input and Output Voltage Sources 26 Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 VG inINPUT VG +VIN V+ RS1 * * enINPUT 4kTRS1 FB x1 RF +RG * inINPUT VOUT RG (Noiseless) ICORE 4kTRF * eO iinOUTPUT -RG VREF x1 RF enOUTPUT * enINPUT iniOUTPUT * -VIN 4kTRF VRS2 inINPUT GND * 4kTRS2 Figure 93. Full Noise Model THERMAL ANALYSIS The VCA822 does not require heatsinking or airflow in most applications. The maximum desired junction temperature sets the maximum allowed internal power dissipation as described in this section. In no case should the maximum junction temperature be allowed to exceed +150°C. Operating junction temperature (TJ) is given by Equation 12: TJ = TA + PD ´ qJA (12) The total internal power dissipation (PD) is the sum of quiescent power (PDQ) and additional power dissipated in the output stage (PDL) to deliver load power. Quiescent power is simply the specified no-load supply current times the total supply voltage across the part. PDL depends on the required output signal and load; for a grounded resistive load, however, it is at a maximum when the output is fixed at a voltage equal to one-half of either supply voltage (for equal bipolar supplies). Under this worst-case condition, PDL = VS2/(4 × RL), where RL is the resistive load. Note that it is the power in the output stage and not in the load that determines internal power dissipation. As a worst-case example, compute the maximum TJ using a VCA822ID (SO-14 package) in the circuit of Figure 77 operating at maximum gain and at the maximum specified ambient temperature of +85°C. PD = 10V(38mA) + 52/(4 ´ 100W) = 442.5mW (13) Maximum TJ = +85°C + (0.449W ´ 80°C/W) = 120.5°C (14) This maximum operating junction temperature is well below most system level targets. Most applications should be lower because an absolute worst-case output stage power was assumed in this calculation of VCC/2, which is beyond the output voltage range for the VCA822. Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 27 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 BOARD LAYOUT Achieving optimum performance with a high-frequency amplifier such as the VCA822 requires careful attention to printed circuit board (PCB) layout parasitics and external component types. Recommendations to optimize performance include: a) Minimize parasitic capacitance to any ac ground for all of the signal I/O pins. This recommendation includes the ground pin (pin 2). Parasitic capacitance on the output can cause instability: on both the inverting input and the noninverting input, it can react with the source impedance to cause unintentional band limiting. To reduce unwanted capacitance, a window around the signal I/O pins should be opened in all of the ground and power planes around those pins. Otherwise, ground and power planes should be unbroken elsewhere on the board. Place a small series resistance (greater than 25Ω) with the input pin connected to ground to help decouple package parasitics. b) Minimize the distance (less than 0.25”) from the power-supply pins to high-frequency 0.1µF decoupling capacitors. At the device pins, the ground and power plane layout should not be in close proximity to the signal I/O pins. Avoid narrow power and ground traces to minimize inductance between the pins and the decoupling capacitors. The power-supply connections should always be decoupled with these capacitors. Larger (2.2µF to 6.8µF) decoupling capacitors, effective at lower frequencies, should also be used on the main supply pins. These capacitors may be placed somewhat farther from the device and may be shared among several devices in the same area of the PCB. c) Careful selection and placement of external components preserve the high-frequency performance of the VCA822. Resistors should be a very low reactance type. Surface-mount resistors work best and allow a tighter overall layout. Metal-film and carbon composition, axially-leaded resistors can also provide good high-frequency performance. Again, keep the leads and PCB trace length as short as possible. Never use wire-wound type resistors in a high-frequency application. Because the output pin is the most sensitive to parasitic capacitance, always position the series output resistor, if any, as close as possible to the output pin. Other network components, such as inverting or non-inverting input termination resistors, should also be placed close to the package. 28 d) Connections to other wideband devices on the board may be made with short direct traces or through onboard transmission lines. For short connections, consider the trace and the input to the next device as a lumped capacitive load. Relatively wide traces (50mils to 100mils, or 1.27mm to 2.54mm) should be used, preferably with ground and power planes opened up around them. e) Socketing a high-speed part like the VCA822 is not recommended. The additional lead length and pin-to-pin capacitance introduced by the socket can create an extremely troublesome parasitic network, which can make it almost impossible to achieve a smooth, stable frequency response. Best results are obtained by soldering the VCA822 onto the board. INPUT AND ESD PROTECTION The VCA822 is built using a very high-speed complementary bipolar process. The internal junction breakdown voltages are relatively low for these very small geometry devices. These breakdowns are reflected in the Absolute Maximum Ratings table. All pins on the VCA822 are internally protected from ESD by means of a pair of back-to-back reverse-biased diodes to either power supply, as shown in Figure 94. These diodes begin to conduct when the pin voltage exceeds either power supply by about 0.7V. This situation can occur with loss of the amplifier power supplies while a signal source is still present. The diodes can typically withstand a continuous current of 30mA without destruction. To ensure long-term reliability, however, diode current should be externally limited to 10mA whenever possible. +VS External Pin ESD protection diodes internally connected to all pins. Internal Circuitry -VS Figure 94. Internal ESD Protection Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 VCA822 www.ti.com SBOS343A – SEPTEMBER 2007 – REVISED OCTOBER 2007 Changes from Original (September 2007) to Revision A ............................................................................................... Page • • • • • • • • • • • Changed GMAX to AVMAX throughout document. ..................................................................................................................... 1 Changed rail quantity for VCA822ID in the Ordering Information table................................................................................. 2 Changed 5th row of AC Performance section in the Electrical Characteristics table............................................................ 3 Changed 4th row of Output section in the Electrical Characteristics table............................................................................ 3 Changed G to AVMAX in conditions of the Electrical Characteristics table.............................................................................. 3 Changed Figure 9, the title of Figure 10, the title of Figure 11, the title of Figure 12, and Figure 13 in the ±5V, DC and Power-Supply Parameters Typical Characteristics......................................................................................................... 6 Changed Figure 14, Figure 21, Figure 23, Figure 25, and Figure 31 in the ±5V, AVMAX = +2V/V Typical Characteristics ... 7 Changed Figure 36, Figure 52, and Figure 56 in the ±5V, AVMAX = +10V/V Typical Characteristics. ................................. 11 Changed Figure 57 and Figure 76 in the ±5V, AVMAX = +100V/V Typical Characteristics................................................... 15 Changed 2200V/µs to 1700V/µs in first paragraph of the Wideband Variable Gain Amplifier Operation section............... 19 Changed Table 2 in the Demonstration Boards section. ..................................................................................................... 23 Submit Documentation Feedback Copyright © 2007, Texas Instruments Incorporated Product Folder Link(s): VCA822 29 PACKAGE OPTION ADDENDUM www.ti.com 8-Oct-2007 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Drawing Pins Package Eco Plan (2) Qty VCA822ID ACTIVE SOIC D 14 50 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA822IDG4 ACTIVE SOIC D 14 50 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA822IDGSR ACTIVE MSOP DGS 10 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA822IDGSRG4 ACTIVE MSOP DGS 10 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA822IDGST ACTIVE MSOP DGS 10 250 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA822IDGSTG4 ACTIVE MSOP DGS 10 250 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA822IDR ACTIVE SOIC D 14 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR VCA822IDRG4 ACTIVE SOIC D 14 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR Lead/Ball Finish MSL Peak Temp (3) (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release. In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis. Addendum-Page 1 PACKAGE MATERIALS INFORMATION www.ti.com 8-Oct-2007 TAPE AND REEL BOX INFORMATION Device Package Pins Site Reel Diameter (mm) Reel Width (mm) A0 (mm) B0 (mm) K0 (mm) P1 (mm) W Pin1 (mm) Quadrant VCA822IDGSR DGS 10 SITE 41 330 12 5.3 3.4 1.4 8 12 Q1 VCA822IDGST DGS 10 SITE 41 180 12 5.3 3.4 1.4 8 12 Q1 VCA822IDR D 14 SITE 41 330 16 6.5 9.0 2.1 8 16 Q1 Pack Materials-Page 1 PACKAGE MATERIALS INFORMATION www.ti.com 8-Oct-2007 Device Package Pins Site Length (mm) Width (mm) VCA822IDGSR DGS 10 SITE 41 346.0 346.0 29.0 VCA822IDGST DGS 10 SITE 41 190.0 212.7 31.75 VCA822IDR D 14 SITE 41 346.0 346.0 33.0 Pack Materials-Page 2 Height (mm) IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, modifications, enhancements, improvements, and other changes to its products and services at any time and to discontinue any product or service without notice. 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